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W.Kucewicz VLSICirciuit Design 1
3.0CMOS Transitors
3.0CMOS Transitors
W.Kucewicz VLSICirciuit Design 2
CMOS TransistorCMOS TransistorCMOS Transistor
CrossCross--section of NMOS Transistorsection of NMOS Transistor
Bulk (Body)
Source Drain
Gate
p
n+
WW
LL
G
S DB
G
S D
NMOS transistor symbol NMOS transistor symbol W W –– width of gatewidth of gateL L -- length of gatelength of gate
W.Kucewicz VLSICirciuit Design 3
CMOS TransistorCMOS TransistorCMOS Transistor
CrossCross--section of PMOS Transistorsection of PMOS Transistor
Bulk (Body)
Source Drain
Gate
n
p+
G
S DB
G
S D
PMOS transistor symbol PMOS transistor symbol
W.Kucewicz VLSICirciuit Design 4
Threshold VoltageThreshold Voltage
W.Kucewicz VLSICirciuit Design 5
CMOS TransistorCMOSCMOS TransistorTransistor
Bulk
Source DrainGate
p
n+
- VGS +
n+
n n channelchannel
W.Kucewicz VLSICirciuit Design 6
The Threshold VoltageThe Threshold VoltageThe Threshold Voltage
Bulk
Source DrainGate
p
n+
- VGS +
n+
nn--channelchannel
W.Kucewicz VLSICirciuit Design 7
The Threshold VoltageThe Threshold VoltageThe Threshold Voltage
The Threshold Voltage The Threshold Voltage is function of several components: oxide thickness, is function of several components: oxide thickness, Fermi voltage, charge of impurities trapped at the surface, dosaFermi voltage, charge of impurities trapped at the surface, dosage of ge of implanted ions, etc.implanted ions, etc.
VVTT = V= VT0T0 + + γγ((√√||--22φφFF + V+ VSBSB| | -- √√||--22φφFF|)|)wherewhere
VVT0T0 is the is the threshold voltage at Vthreshold voltage at VSBSB = 0= 0 and is mostly aand is mostly a function of the manufacturing processfunction of the manufacturing process
φφFF = = -- φφTT ln(Nln(NAA /n/nii)) is the is the Fermi potentialFermi potentialφφTT = kT/q = 26mV at= kT/q = 26mV at 300K is the thermal voltage; N300K is the thermal voltage; NAA is the acceptor ion concentration;is the acceptor ion concentration; nnii ≈≈
1.5x101.5x101010 cmcm--33 at 300K is the intrinsic carrier concentration inat 300K is the intrinsic carrier concentration in pure silicon)pure silicon)
γγ = = √√(2q(2qεεsisi NNAA )/C)/Coxox is the is the bodybody--effect coefficienteffect coefficient (impact of(impact of changes in Vchanges in VSBSB ) )
εεsisi == 1.053x101.053x10--1010 F/m is the permittivity of silicon;F/m is the permittivity of silicon;
CCoxox = = εεoxox/t/toxox is the gate oxide capacitance withis the gate oxide capacitance with εεoxox == 3.5x103.5x10--1111 F/mF/m
W.Kucewicz VLSICirciuit Design 8
The Body EffectThe The Body Body EffectEffect
VVBSBS(V)(V)
VVTT(V)(V)VVSBSB is the substrateis the substrate bias bias
voltage (normallyvoltage (normally positive positive for nfor n--channelchannel devices with devices with the bodythe body tied to ground)tied to ground)
A negative biasA negative bias on thesubstrate causes Vcauses VTT to to increaseincrease from 0.45V to from 0.45V to 0.85V0.85V
W.Kucewicz VLSICirciuit Design 9
CharacteristicsCharacteristics
W.Kucewicz VLSICirciuit Design 10
Transistor in Linear ModeTransistor in Linear ModeTransistor in Linear Mode
n+ n+
SourceDrain
Gate
p
- VGS + VDS +
ID
Bulk
- V(x) +
x
VGS > VTVVGSGS > V> VTT
W.Kucewicz VLSICirciuit Design 11
Transistor in Linear ModeTransistor in Linear ModeTransistor in Linear ModeFor longFor long--channel devices (L > 0.25 micron)channel devices (L > 0.25 micron)
When VWhen VDSDS ≤≤ VVGSGS –– VVTT
IIDD = k’= k’nn W/L [(VW/L [(VGSGS –– VVTT )V)VDSDS –– VVDSDS22 /2]/2]
wherewhere
k’k’nn = = µµnn CCoxox = = µµnn εεoxox/t/toxox = is the = is the processprocess transconductance transconductance parameterparameter ((µµnn is the carrier mobilityis the carrier mobility (m(m22/Vsec))/Vsec))
kknn = k’= k’nn W/L is the W/L is the gain factorgain factor of the deviceof the device
For small VFor small VDSDS , there is a linear dependence between V, there is a linear dependence between VDSDS
and Iand IDD , hence the name , hence the name resistiveresistive or or linearlinear regionregion
W.Kucewicz VLSICirciuit Design 12
Transistor in Saturation ModeTransistor in Saturation ModeTransistor in Saturation Mode
n+ n+
SourceDrain
Gate
p
- VGS +
+
ID
Bulk
VDS > VGS-VT
VGS - VT =VDS
PinchPinch--offoff
W.Kucewicz VLSICirciuit Design 13
Transistor in Saturation ModeTransistor in Saturation ModeTransistor in Saturation Mode
For long channel devicesFor long channel devices
When VWhen VDSDS ≥≥ VVGSGS –– VVTT
IIDD = k’= k’nn/2 W/L [(V/2 W/L [(VGSGS –– VVTT))22]]since the voltage difference over the induced channelsince the voltage difference over the induced channel(from the (from the pinchpinch--offoff point to the source) remains fixed atpoint to the source) remains fixed atVVGSGS –– VVTT
However, the effective length of the conductive channelHowever, the effective length of the conductive channelis modulated by the applied Vis modulated by the applied VDSDS , so, so
IIDD‘ = I‘ = IDD (1 + (1 + λλVVDSDS ))
where where λλ is the is the channelchannel--length modulationlength modulation (varies with the(varies with theinverse of the channel length)inverse of the channel length)
W.Kucewicz VLSICirciuit Design 14
ID Current ParametersIIDD Current ParametersCurrent Parameters
For a fixed VFor a fixed VDSDS and Vand VGSGS (> V(> VTT ), I), IDSDS is a function ofis a function of
the distance between the source and drain the distance between the source and drain –– LL
the channel width the channel width –– WW
the threshold voltage the threshold voltage –– VVTT
the thickness of the SiOthe thickness of the SiO22 –– ttoxox
the dielectric of the gate insulator (SiOthe dielectric of the gate insulator (SiO22 ) ) –– εεoxox
the carrier mobilitythe carrier mobilityfor for NMOSNMOS:: µµnn = 500 cm= 500 cm22/Vsec/Vsec
for for PMOSPMOS: : µµpp = 180 cm= 180 cm22/Vsec/Vsec
W.Kucewicz VLSICirciuit Design 15
Short channel effect
Short channel effect
W.Kucewicz VLSICirciuit Design 16
Short Channel EffectsShort Channel EffectsShort Channel EffectsBehavior of short channel device mainly due toBehavior of short channel device mainly due to
Velocity saturationVelocity saturation–– the velocity of the carriers the velocity of the carriers saturates due to scattering saturates due to scattering (collisions suffered by the carriers)(collisions suffered by the carriers)
-- the velocity can be express bythe velocity can be express by::
ConstantConstantvelocityvelocity
Constant mobilityConstant mobility
(slope = (slope = µµ))
For an NMOS device with L of 1For an NMOS device with L of 1µµm, only a couple of voltsm, only a couple of voltsdifference between D and S are needed to reach velocitydifference between D and S are needed to reach velocity
saturationsaturation
ξξ ≤≤ ξξc c υυ = = µµ •• ξξ/(1+ /(1+ ξξ//ξξcc))
ξξ ≥≥ ξξc c υυ = = υυSat Sat == µµ •• ξξcc/2/2
W.Kucewicz VLSICirciuit Design 17
Velocity saturationVelocity saturationVelocity saturation
For short channel devicesFor short channel devices
Linear: When VLinear: When VDSDS ≤≤ VVGSGS –– VVTT
IIDD = k(V= k(VDSDS ) k’) k’nn W/L [(VW/L [(VGSGS –– VVTT )V)VDSDS –– VVDSDS22 /2]/2]
wherewhere
k(V) = 1/(1 + (V/k(V) = 1/(1 + (V/ξξcc L)) is a measure of the degree ofL)) is a measure of the degree of velocity saturationvelocity saturation
Saturation: When VSaturation: When VDSDS = V= VDSatDSat = = LL ξξcc == 2L2LυυSatSat// µµ
IIDSatDSat = = υυSatSat CCoxoxW [VW [VGSGS –– VVTT –– VVDsatDsat/2/2]]
W.Kucewicz VLSICirciuit Design 18
Velocity Saturation EffectVelocity Saturation EffectVelocity Saturation EffectFor short channel devicesFor short channel devices and large enough Vand large enough VGSGS –– VVTT
VVDSatDSat < V< VGSGS –– VVTT soso the the device entersdevice enters saturation saturation before before VVDSDS reaches Vreaches VGSGS –– VVTTandand operates more often inoperates more often insaturationsaturation
IIDSatDSat has a has a linear dependencelinear dependence in function of Vin function of VGSGS so a so a reduced amount of current is delivered for a given control reduced amount of current is delivered for a given control voltagevoltage
W.Kucewicz VLSICirciuit Design 19
Long Channel NMOSLong Channel Long Channel NMOSNMOS
LinearLinear SaturationSaturation
IIDD[A][A]
Qua
dQ
uad r
atic
rati
cde
pend
ence
depe
nden
ce
CutCut--offoff
VVDSDS [V][V]
NMOS transistor, 0.25um, NMOS transistor, 0.25um, LLdd = 10um= 10um, W/L = 1.5, V, W/L = 1.5, VDDDD = 2.5V, V= 2.5V, VTT = 0.4V= 0.4V
W.Kucewicz VLSICirciuit Design 20
Short channel NMOS Short channel Short channel NMOS NMOS
IIDD[[AA]]
Line
arLi
near
depe
nden
cede
pend
ence
VVDSDS [[VV]]
NMOS transistor, 0.25um, NMOS transistor, 0.25um, LLdd = 0.25um= 0.25um, W/L = 1.5, V, W/L = 1.5, VDDDD = 2.5V, V= 2.5V, VTT = 0.4V= 0.4V
W.Kucewicz VLSICirciuit Design 21
ID vs. VGS CharacteristicsIIDD vsvs. V. VGSGS CharacteristicsCharacteristicsLinear (shortLinear (short--channel)channel) versus quadratic (longversus quadratic (long--channel) channel)
dependence ofdependence of IIDD on Von VGSGS in saturationin saturation
VelocityVelocity saturationsaturationcauses the shortcauses the short--channel channel device todevice to saturate at saturate at substantiallysubstantially smaller smaller values of Vvalues of VDSDS resulting in resulting in a substantiala substantial drop in drop in current drivecurrent drive
(for V(for VDSDS = 2.5V,= 2.5V, W/L = 1.5)W/L = 1.5)
0 0.5 1 1.5 2 2.5VVGSGS [[VV]]
IIDD[m[mAA]]0.60.6
0.50.5
0.40.4
0.30.3
0.20.2
0.10.1
0.00.0
W.Kucewicz VLSICirciuit Design 22
Short channel PMOS Short channel Short channel PMOS PMOS All polarities of all voltages and currents are reversedAll polarities of all voltages and currents are reversed
VVDSDS [[VV]]
IIDD[[AA]]
Due to the smaller Due to the smaller mobility, the maximummobility, the maximumcurrent is current is only 42%only 42% of of what is achieved by a what is achieved by a similarsimilar NMOS transistor.NMOS transistor.
PPMOS transistor, 0.25um, MOS transistor, 0.25um, LLdd = 0.25um= 0.25um, W/L = 1.5, V, W/L = 1.5, VDDDD = = --2.5V, V2.5V, VTT = = --0.4V0.4V
W.Kucewicz VLSICirciuit Design 23
Subthreshold ConductanceSubthreshold ConductanceSubthreshold Conductance
Transition from ONTransition from ON to OFF to OFF is gradualis gradual (decays (decays exponentially)exponentially)
Current rollCurrent roll--off isoff is also also affected byaffected by increase in increase in temperaturetemperature
Has repercussions inHas repercussions indynamic circuits and fordynamic circuits and for power power consumptionconsumption
W.Kucewicz VLSICirciuit Design 24
MOS ModelsMOS Models
W.Kucewicz VLSICirciuit Design 25
MOS transistor First Order ModelMOS MOS transistor Firsttransistor First Order ModelOrder Model
The IThe Idsds current SPICE caclulation is based current SPICE caclulation is based on 6 on 6 parametersparameters: :
0.25µm0.25µmMOS channel lengthL
0.5-40µm0.5-20µmMOS channel widthW
0.4 V0.50.4 V0.5Bulk threshold parameterGAMMA (γ)
0.3V0.3VSurface potential at strong inversionPHI (ϕ)
120µA/V2300µA/V2Transconductance coefficientKP (KP)
-0.4V0.4VTheshold voltageVTO (VTO)
pMOSnMOS
TYPICAL VALUE 0.25µmDEFINITIONPARAMETER
W.Kucewicz VLSICirciuit Design 26
MOS transistor First Order ModelMOS MOS transistor Firsttransistor First Order ModelOrder Model
Long channel Long channel ((1010µµmm) ) MeasuredSimulated
Simulation results ofSimulation results of nMOSnMOS transistor usingtransistor using model 1model 1
The MOS model 1 works The MOS model 1 works fine in fine in micron technologymicron technology
W.Kucewicz VLSICirciuit Design 27
MOS transistor First Order ModelMOS MOS transistor Firsttransistor First Order ModelOrder ModelSimulation results ofSimulation results of nMOSnMOS transistor usingtransistor using model 1model 1
Short channel Short channel (0.(0.2525µµmm) )
Measured
Simulated
150% error150% error
The The MOS model 1 MOS model 1 is is far a far a way in submicron technologyway in submicron technology
W.Kucewicz VLSICirciuit Design 28
MOS transistor Third Order ModelMOS MOS transistor Thirdtransistor Third Order ModelOrder Model
The IThe Idsds current SPICE calcurrent SPICE calcculation take into account a set ulation take into account a set of physical limitations in semiof physical limitations in semi--empirical way: empirical way:
0.07 V-10.07 V-1Substhreshold factorNSS
0.3 V-10.3 V-1Mobility degradation factorTHETA
100Km/s150Km/sMaximum drift velocityVMAX
0.01 V-10.01 V-1Saturation field factorKAPPA
0.01µm0.01µmLateral diffusion into channelLD
pMOSnMOS
TYPICAL VALUE 0.25µmDEFINITIONPARAMETER
W.Kucewicz VLSICirciuit Design 29
MOS transistor Third Order ModelMOS MOS transistor Thirdtransistor Third Order ModelOrder ModelSimulation results ofSimulation results of nMOSnMOS transistor 10x0transistor 10x0..2525µµm m
using using model 3model 3
MOS level 3 includes short channel limitation effectsMOS level 3 includes short channel limitation effects
W.Kucewicz VLSICirciuit Design 30
BSIM4 Berkeley MOS ModelBSIMBSIM4 4 BerkeleyBerkeley MOS ModelMOS ModelBBerkeley SShort-channel IIGFET MModel
20 Basic 20 Basic parametersparameters
60 secondary 60 secondary parametersparameters
2220 fitting 20 fitting parametersparameters
W.Kucewicz VLSICirciuit Design 31
BSIM4 Berkeley MOS ModelBSIMBSIM4 4 BerkeleyBerkeley MOS ModelMOS Model
•• BSIM4 has been introduced BSIM4 has been introduced in in 20002000
•• Provides Provides a a perfect perfect continuity between lenear continuity between lenear ans ans saturated regionssaturated regions
•• Model gourousModel gourous
•• Model is becoming a serviceModel is becoming a service
Achieve good fit with static measurements using Achieve good fit with static measurements using a wide set of tricks and internal arrangementsa wide set of tricks and internal arrangements
W.Kucewicz VLSICirciuit Design 32
MOS ModelMOS ModelMOS Model
BSIM4 thresholdBSIM4 threshold voltagevoltage modelmodel
DIBLNULDSCEss VtVtVtVbsKVbsKVTHOvth ∆+∆+∆+−Φ−−Φ+= .2)(.1
Short channel effects
Vth (V)
Channel length (µm)
W.Kucewicz VLSICirciuit Design 33
MOS ModelMOS ModelMOS Model
BSIM4 BSIM4 IIDS DS modelmodel
)Lε
V(1
V)4.vt)(2V
VA(1VεεµeffLeffWeffIds0
effsat
dseff
dseff
gsteff
dseffbulkgsteff
r0
++−=
TOXE
Ids
Vgs (V)
Ids (Log)
Vds (V)
W.Kucewicz VLSICirciuit Design 34
MOS transistor BSIM4 ModelMOS MOS transistor BSIM4transistor BSIM4 ModelModel
Simulation results ofSimulation results of nMOSnMOS transistor 10x0transistor 10x0..1212µµm using different modelsm using different models
Model1Model1 Model3Model3 BSIM4BSIM4
W.Kucewicz VLSICirciuit Design 35
MOS ModelMOS ModelMOS Model
Poor fitPoor fitWidth (µm)100.0
10.0
0.0 2.5 5.0 10
1.0
7.5
The MOS model is reliable within its optimized rangeThe MOS model is reliable within its optimized range
Good fitGood fitLength (µm)
W.Kucewicz VLSICirciuit Design 36
The MOS Current Source ModelThe The MOS MOS Current SourceCurrent Source ModelModel
IIDD = 0 for V= 0 for VGSGS –– VVTT ≤≤ 00
IIDD = k’ W/L [(V= k’ W/L [(VGSGS –– VVTT )V)Vminmin ––VVminmin22/2](1+/2](1+λλVVDSDS ))
for Vfor VGSGS –– VVTT ≥≥ 00
with Vwith Vminmin = min(V= min(VGSGS –– VVTT , V, VDSDS , V, VDSatDSat))
Determined by the voltages at the four terminals Determined by the voltages at the four terminals andand a set of five device parametersa set of five device parameters0.250.25µµmm
W.Kucewicz VLSICirciuit Design 37
The MOS Model as a SwitchThe The MOS Model as a MOS Model as a SwitchSwitch
Resistance inverselyResistance inverselyproportional to W/L (doublingproportional to W/L (doublingW halves RW halves Ronon ))
For VFor VDDDD >>V>>VTT +V+VDSatDSat/2, R/2, Rononindependent of Vindependent of VDDDD
Once VOnce VDDDD approaches Vapproaches VTT ,,RRonon increases dramaticallyincreases dramatically
Modeled as a switch withModeled as a switch with infinite off resistance and ainfinite off resistance and afinite on resistance, Rfinite on resistance, Ronon
W.Kucewicz VLSICirciuit Design 38
Switch Model of nMOS TransistorSwitchSwitch ModelModel ofof nMOSnMOS TransistorTransistor
W.Kucewicz VLSICirciuit Design 39
Switch Model of nMOS TransistorSwitchSwitch ModelModel ofof nMOSnMOS TransistorTransistor
Input Logic signal
Output Logic signal
Switch
TheThe nMOSnMOS drives well drives well O but O but poorly high voltage poorly high voltage ((VVDDDD--VVTT))
W.Kucewicz VLSICirciuit Design 40
Switch Model of pMOS TransistorSwitchSwitch MMoodeldel ofof pMOSpMOS TransistorTransistor
W.Kucewicz VLSICirciuit Design 41
Switch Model of pMOS TransistorSwitchSwitch ModelModel ofof pMOSpMOS TransistorTransistor
Input Logic signal
Output Logic signal
Switch
TheThe pMOSpMOS drives well high voltagedrives well high voltage but but poorly poorly zero (zero (VVTT))
W.Kucewicz VLSICirciuit Design 42
MOS CapacitancesMOS Capacitances
W.Kucewicz VLSICirciuit Design 43
MOS Gate CapacitancesMOS MOS Gate CapacitancesGate Capacitances
Capacitance of Gate Capacitance of Gate to to ChannelChannel
CCGG = = CCGCGC + + CCGS0GS0 + + CCGD0GD0
= = CCGCGC ++ 2C2CoxoxxxddW W
CCGCGC = = CCGCBGCB+ + CCGCSGCS+ + CCGCDGCD
wherewhereCCoxox = = εεoxox//ttoxox
CCGCBGCB –– cap.cap. gategate to bodyto body
CCGCSGCS –– cap.cap. gategate to to sourcesource
CCGCDGCD –– cap.cap. gategate to to draindrain
W.Kucewicz VLSICirciuit Design 44
MOS Gate CapacitancesMOS MOS Gate CapacitancesGate Capacitances
CutCut--offoff LinearLinear SaturationSaturation
W.Kucewicz VLSICirciuit Design 45
MOS Gate CapacitancesMOS MOS Gate CapacitancesGate Capacitances
CutCut--offoff
2 CoxWL/3 + 2 CoxxdW2 CoxWL/302 CoxWL/30SaturationSaturation
CoxWL + 2 CoxxdWCoxWLCoxWL/2CoxWL/20LinearLinear
CoxWL + 2 CoxxdWCoxWL00CoxWLCutoffCutoff
CCGGCCGCGCCCGCDGCDCCGCSGCSCCGCBGCBOperationOperation
regionregion
LinearLinear SaturationSaturation
W.Kucewicz VLSICirciuit Design 46
MOS Structure CapacitancesMOSMOS Structure CapacitancesStructure CapacitancesJunction CapacitancesJunction Capacitances
CCdiffdiff = = CCbottombottom + + CCside walls side walls = = CCjjLLSSW W + + CCjswjsw((2L2LSS+W)+W)
W.Kucewicz VLSICirciuit Design 47
MOS Structure CapacitancesMOSMOS Structure CapacitancesStructure CapacitancesMOSFET capacitance model.MOSFET capacitance model.
CCGSGS = = CCGCSGCS + + CCGS0GS0
CCGDGD = = CCGCDGCD + + CCGD0GD0
CCGBGB = = CCGCBGCB
CCSBSB = = CCSdiffSdiff
CCDBDB = = CCDdiffDdiff
W.Kucewicz VLSICirciuit Design 48
MOS Structure CapacitancesMOSMOS Structure CapacitancesStructure CapacitancesConsider an NMOS transistor with
the following parameters: tox = 6 nm, L = 0.24 µm, W = 0.36 µm, LD = LS = 0.625 µm, CO = 3 x10–10 F/m, Cj0 = 2 x10–3 F/m2 , Cjsw0 = 2.75 x10–10 F/m. Determine the zero-bias value of all
relevant capacitances.CCGBGB = εoxLW/tox = 0.5fF0.5fFCCGSGS = C= CGDGD= C0W = 0.1 0.1 fFfFCCSB SB = C= CDBDB = Cj0WLS,D+Cjsw0(W+2LD,S)=0.45fF+0.44fF= 0.89 0.89 fFfF
0.250.25µµmm
W.Kucewicz VLSICirciuit Design 49
MOS Source-Drain ResistanceMOS MOS SourceSource--Drain ResistanceDrain Resistance
W.Kucewicz VLSICirciuit Design 50
Other effectsOther effects
W.Kucewicz VLSICirciuit Design 51
Other Submicron MOS Transistor Concerns
Other Submicron Other Submicron MOS MOS Transistor Transistor ConcernsConcerns
Velocity saturationVelocity saturation
Subthreshold conductionSubthreshold conductionTransistor is already partially conducting for voltages below VTransistor is already partially conducting for voltages below VTT
Parasitic resistancesParasitic resistances-- resistances associated with theresistances associated with the source source
and drain contactsand drain contacts
W.Kucewicz VLSICirciuit Design 52
Other Submicron MOS Transistor Concerns
Other Submicron Other Submicron MOS MOS Transistor Transistor ConcernsConcerns
Threshold variationsThreshold variations-- In longIn long--channel devices, the threshold is a function of the lengthchannel devices, the threshold is a function of the length(for low V(for low VDSDS))-- In shortIn short--channel devices, there is a drainchannel devices, there is a drain--induced thresholdinduced thresholdbarrier lowering at the upper end of the Vbarrier lowering at the upper end of the VDSDS range (for low L)range (for low L)
W.Kucewicz VLSICirciuit Design 53
Other Submicron MOS Transistor Concerns
Other Submicron Other Submicron MOS MOS Transistor Transistor ConcernsConcerns
LatchLatch--up.up.TheThe combination of wells and substratescombination of wells and substrates results in the formation of results in the formation of parasitic nparasitic n--pp--nn--p p structuresstructures ((thyristor thyristor !!)!!)
TTo avoid latchup, theo avoid latchup, the resistances resistances RRnwellnwell and and RRpsubspsubs should be minimized. should be minimized.
This can be achieved by providingThis can be achieved by providing numerous well and substrate contacts, numerous well and substrate contacts, placed close to the source connections of theplaced close to the source connections of the NMOS/PMOS devices.NMOS/PMOS devices.
W.Kucewicz VLSICirciuit Design 54
Other Submicron MOS Transistor Concerns
Other Submicron Other Submicron MOS MOS Transistor Transistor ConcernsConcerns
HotHot--Carrier EffectsCarrier EffectsCause the Cause the II--V V Characteristics of an Characteristics of an NMOS NMOS transistor transistor to to degrade degrade from extensive usagefrom extensive usage
W.Kucewicz VLSICirciuit Design 55
ConclusionsConclusionsConclusions
The MOS(FET) transistor is a voltage-controlled device, where the controlling gate terminal is insulated from the conducting channel by a SiO2 capacitor.
Based on the value of the gate-source voltage with respect to a threshold voltage VT , three operationregions have been identified: cut-off, linear, and saturation.
The MOS transistor, approximates a voltage-controlled switch: when the control voltage is low, the switch is nonconducting (open); for a high control voltage, a conducting channel is formed, and the switch can be considered closed. This two-state operation matches the concepts of binary digital logic.
W.Kucewicz VLSICirciuit Design 56
ConclusionsConclusionsConclusionsThe continuing reduction of the device dimensions to
the submicron range has introduced some substantial deviations from the traditional long-channel MOS transistor model.
The most important one is the velocity saturation effect, which changes the dependence of the transistor current with respect to the controlling voltage fromquadratic to linear.
One particular effect that is gaining in importance is the sub-threshold conduction, which causes devices to conduct current even when the control voltage drops below the threshold.
W.Kucewicz VLSICirciuit Design 57
ConclusionsConclusionsConclusions
The dynamic operation of the MOS transistor is dominated by the device capacitors. The main contributors are the gate capacitance and the capacitance formed by the depletion regions of the source and drain junctions. The minimization of thesecapacitances is the prime requirement in high-performance MOS design.
The MOS transistor is expected to dominate the digital integrated circuit scene for the next decade. Continued scaling will lead to device sizes of approximately 0.07 micron by the year 2010, and logic circuits integrating more than 1 billion transistors on a die.