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7/28/2019 Nltl Emc Fdq
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Modeling of Transmission Lines with EM Wave Coupling by
Finite Difference Quadrature Methods
Qinwei Xu and Pinaki Mazumder
Abstract This paper proposes an efficient numerical approxi-
mation technique, called the Finite Difference Quadrature (FDQ)
Method, which has been adapted to model transmission lines
(TLs) with external EM wave coupling. The finite difference
quadrature method can quickly compute finite differences be-
tween adjacent grid points by estimating a weighted linear sum
of derivatives at a set of points belonging to the domain. Similarly
to the Gaussian Quadrature method to compute the numerical in-
tegrals, FDQ method uses global quadrature method to construct
the approximation framework, however, to compute the finite dif-
ference. A discrete modeling approach, FDQ needs much sparser
grid points than the Finite Difference (FD) methods to achieve
comparable accuracy. The FDQ-based equivalent models can be
integrated into simulators like SPICE to efficiently simulate cir-
cuits involving EM interference. The FDQ procedure can be ap-
plied to solve other classes of partial differential equations. This
paper thus demonstrates a general numerical approach, though
the focus of the paper is transmission line modeling.
1 INTRODUCTION
Fast operation and large integration scale have made
the interconnect effect an important issue in high-speed
systems. In addition to the on-chip and on-board ef-
fects of delay, crosstalk, and reflections, electrically
long interconnects pose the antenna effect, as they
receive considerable dose of incident electromagnetic(EM) waves emitted by external electronic devices [1].
Fast clocking rate and short rise time result in sig-
nals with wavelengths comparable to interconnect sizes
which increases the radiation efficiency of the conduct-
ing traces, while small feature sizes lead to high electro-
magnetic interference (EMI) susceptibility among the
circuit parts. The antenna effect becomes a more seri-
ous challenge to signal integrity with progressive
scaling.
Equivalent source modeling, based on the quasi-TEM
assumption, is one of the mainstream approaches to
solve the problem of external field coupling to TLs [2],
in which incident EM waves illuminating the TLs aremodeled as equivalent sources. These effects of the in-
cident field appear as forcing functions on the TL equa-
tions, which are incorporated into the circuit simulators
altogether with other devices. Compared to the field
solvers, the equivalent circuit approach is computation-
ally efficient and numerically accurate as long as the
quasi-TEM assumption is valid. The equivalent source
approach in the literature [3] is mathematically based on
This work was supported by MURI grant.
EECS Dept., University of Michigan, Ann Arbor, MI 48109-
2122, Email:
qwxu,mazum
@eecs.umich.edu
0
i
j
zj
zi
yj
yi
- xA0(x,0,0)
Aj(x,yj,zj)
Ai(x,yi,zi)z
yEH
d
E
H
E
Figure 1: MTL illuminated by EM wave.
the finite difference (FD) methods. As the FD methods
have low order accuracy, the electrical length of each
section has to be a considerably small fraction (1/12-
1/20) of the minimum wave length of the signal; there-
fore, the equivalent models consist a excessive number
of lumped elements. On the other hand, numerical in-
tegration (quadrature) is more stable and reliable than
differentiation because it globally integrates the local
information. Integral approaches like Gaussian Quadra-
ture generally give more accurate solutions [4]. In thispaper, the Finite Difference Quadrature (FDQ) method
is proposed to model TLs. The idea of the FDQ method
is to quickly compute the finite difference of two neigh-
boring grid points by estimating a weighted linear sum
of derivatives at a small set of points belonging to the
domain. The weighted linear sum is like the numeri-
cal integral in Gaussian Quadrature method, yet it is to
compute finite differences rather than the integrals. As
a result, FDQ needs much sparser grid points than the
Finite Difference (FD) methods to achieve comparable
accuracy.
2 QUASI-TEM FORMULATIONS OF TLSWITH EM WAVE COUPLING
The quasi-TEM assumption of TLs is equivalent to the
condition that the dimensions of TLs cross-sectional
sizes are much smaller than a wavelength of the ex-
ternal EM wave. Under such a condition, the principal
propagation mode of the TLs is TEM, and can be ac-
curately described by the Telegraphers equations. The-
oretical analysis and experimental results have shown
that the external EM wave illuminating can be modeled
as forcing terms which are added in the Telegraphers
equations [1]. Let the illuminating EM wave be repre-
7/28/2019 Nltl Emc Fdq
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sented in the Cartesian coordinate system by
!
"
#
%
!
"
% #
'
!
"
' ) (1)
and the TLs stretch along0
direction. Assume that
the reference of conductor (defined as line 0) is colin-ear with the
0-axis (see Fig.1). By assuming a quasi-
TEM mode of propagation along an MTL consisting of 1
# 3
conductors, the voltages5
0
)
and currents6
0
)
along the conductors can be represented by the
-domain Telegraphers equations:
8
8
0
5
0
)
#
9
0
6
0
)
# B
0
6
0
)
5 E
0
)
(2)8
8
0
6
0
)
#
G
0
5
0
)
# I
0
5
0
)
6
E
0
)
(3)
where9
0
,G
0
, B
0
and I
0
denote the per-unit-
length (PUL) inductance, capacitance, resistance, andconductance
1 R 1
matrices at point 0 , respectively.
The1
-dimensional vector forcing functions5 E
0
) V
and6
E
0
) V
are derived as in [1].
3 FINITE DIFFERENCE QUADRATURE
METHODS
There are two major approaches to numerically solve
partial differential equations (PDEs): one is the numer-
ical finite differencing and the other is the numerical
integration (quadrature). Finite difference (FD) meth-
ods have been fully developed in the literature and are
widely used to numerically solve differential equationsbecause of its simplicity and applicability. Consider a
smooth function X
0
and its derivative function X Y
0
both defined on the domain a b ) 3 d , which is uniformly
divided by grid points e 0 ) f
3 g g h i , then the central
FD framework is given by
X
0
q r
t
X
0
u r
y
X
Y
0
(4)
where
0
q r
t
0
is the distance between two ad-
jacent grid points. This framework is a local approxi-
mation in that the finite difference is only represented
by the immediately neighboring grid points. Despite
its wide popularity and uses, it requires very dense gridpoints and therefore takes computationally prohibitive
time to solve large problems. One the other hand,
the numerical integration is more stable and converges
faster as it globally integrates the local information. The
approximation framework of Gaussion Quadrature can
be adapted as
X
t
X
"
X
Y
0
8
0
r
X
Y
0
) (5)
where
s are the coefficients which are determined by
the orthogonal polynomials in the particular Gaussian
1/N
V0 V1 VN-1 VN
I0 I1/2 I1+1/2 IN-1/2 IN
0 1
...
...
V2
Figure 2: FDQ framework.
rules. Compared to the FD framework in Eqn. 4, the
Gaussian Quadrature in Eqn. 5 is a global approxima-
tion in that the difference between X
and X
"
is rep-
resented by all the grid points over the entire domain.
We propose a new technique called the finite dif-
ference quadrature (FDQ) method to integrate the fi-
nite difference and quadrature methodsin one approach.
The general framework of FDQ is shown by
X
0
q r
t
X
0
r
0
X
Y
0
g (6)
where
s are the FDQ coefficients to be determined,
0
is the weight at point 0 . The RHS representa-
tion of the FDQ Eqn. 6 is apparently a global quadra-
ture approximation, which is the same as the RHS in
the Gaussian Quadrature Eqn. 5; however, the LHS of
Eqn. 6 is the finite difference, compared to the numeri-
cal integral over the entire domain in Eqn. 5. The FDQ
method is as simple and applicable as the finite differ-
ence method, and is as stable and efficient as the quadra-
ture method. It is expected to be able to solve all kinds
of PDEs with higher efficiency. In this paper, we use
the FDQ method to solve the Telegraphers equations
for transmission line modeling.
For simplicity, the FDQ modeling of TLs is first de-
veloped on a uniform two-wire TL with one of the wires
being the reference. In this case, the vectors and matri-
ces in Eqns. 2 and 3 become scalars:
0
)
,
0
)
,
,
,
and
. A direct numerical technique, FDQ
methods do not need to decouple the MTL, therefore its
application to non-uniform and/or multi-conductor TL
is straightforward extended. Assume that a TL has been
normalized to one unit of length along0
direction.
As shown in Fig. 2, the TL is equally discretized to
small sections. There are two sets of grid points: one
set are at integer-spatial positions 0
f ) f
b
g g ,
the other are at half-spatial positions 0 q r k
f #
3
y
) f
b
g g
t
3
. The grid points are num-
bered in such a way that the voltages are evaluated at
integer-spatial positions as
0
)
) f
b
g g
and the currents are evaluated at half-spatial positions
as
q r k
0
q r k
)
) f
b
g g
t
3
. In addition,
the currents o
b
)
and
3 )
are input and
output currents at the port, respectively. For clarity of
the intermediate use in the context, we define the inter-
7/28/2019 Nltl Emc Fdq
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mediate voltages q r k
0
q r k
)
) f
b
g g
t
3
and the intermediate currents
0
)
) f
3 g g
t
3
.
For the finite difference of voltage, the FDQ approx-
imation framework is
q r
t
u r
o
"
8
8
0
q r k
) f
b
g g
t
3
(7)
For the finite difference of current, the FDQ approxi-
mation framework is
q r k
t
u r k
o
8
8
0
) f
3 g g
t
3
(8)
for internal grid points and
r k
t
o
o
o
8
8
0
)
t
u r k
o
8
8
0
(9)
for the left and right boundary, respectively.
Substituting Eqns. 2 and 3 into Eqns. 7-9, we obtain:
q r
t
u r
o
"
a
#
q r k
#
E
0
q r k
)
d
f
b
g g
t
3
) (10)
q r k
t
u r k
o
a
#
#
E
0
)
d )
f
3 g g
t
3
)
(11)
for the internal grid points and
r k
t
o
o
o
a
#
#
E
0
)
d (12)
t
u r k
o
a
#
#
E
0
)
d (13)
for the boundary points.
Eqns. 10-13 are the FDQ approximation framework
of the two-wire TL in
-domain, the coefficients of
which have yet to be determined.Following the concept of Weighting Residual
Method, a testing-function approach of the Galerkins
method is employed by using the following function set:
3 )
0
)
0
k
) g g g )
0
) g g g (14)
The function set constitute a linear vector space
of polynomials with respect to the operations of addi-
tion and multiplication. In order for Eqn. 7 to be exact
in the -dimensional subspace, every item in the base
0
) h
b
g g serves as a test function to fit Eqn. 7. As
a result, an R
matrix of coefficients is obtained as
a
"
d and, similarly, the
# 3
R
# 3
matrix
a
d .
The FDQ approximations in Eqns. 7 and 8-9 re-
spectively have approximation orders of
0
and
0
q r
, compared to the low approximation of FD
methods.
Once the positions of the grid points are given, the
above testing-function approach gives constant FDQ
coefficient matrices, no matter in what applications the
TL equations appear. For the equally spaced grid points,
the coefficients can be calculated and saved for future
use, which reduce the computational cost in practice.
With the pre-calculated coefficient matrices,
Eqns. 10-13 are rewritten as
5
6
!
!
5E
6
E
#
#
!
o
(15)
where
#
)
#
5
a o
rg g g
d
6
a
r k
r q r k
g g g
u r k
d
5 E
a E
0
r k
E
0
r q r k
g g g
E
0
u r k
d
6
E
a E
0o
E
0
r
g g g
E
0
d
is an R
# 3
matrix, and#
is an
# 3
R y
con-
necting matrix of the external exiting current sources:
%'
'
'(
t
3 3
t
3 3
. . .. . .
t
3 3
) 0
0
0
2
)
#
%'
'
'(
3
b
b b
......
b
t
3
) 0
0
0
2
Eqn. 15 can be transformed into and solved in the
time domain. In this paper we will not introduce the
time domain algorithm; instead, we derive the SPICE-
compatible equivalent model from the above equations
for circuit simulation.
4 NUMERICAL RESULTS
The heuristic for the order of FDQ modeling is to takey
voltage differences per wavelength, i.e., y
in
Eqn. 15 per wavelenght (see Fig. 2). It is well estab-
lished that for the finite difference method, a resolu-
tion of more than dozen points per wavelength (PPW) is
needed for required accuracy [4]. Therefore, the resolu-
tions of 4 PPW is a significant improvement, which ap-
proaches the Nyquist limit ofy
PPW. The intrinsic rea-
son for the improvement is the global quadrature with
the Weighting Residual method. The more global a
quadrature framework is, the closer its resolution could
7/28/2019 Nltl Emc Fdq
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B
A
C2
D3
D4D2
D1
C1
0 2 4 6 8 10 120.5
0
0.5
1
1.5
2
Time(ns)
Voltage
(V)
Output w/o EM wave
D1 with EM waveD2 with EM waveD3 with EM waveD4 with EM wave
Figure 3: H clock tree with EM wave interference.
approach the Nyquist limit to achieve the required ac-
curacy. The globality of FDQ approximation frame-
work heuristically makes it one of the approaches which
closely approach the Nyquist limit.
The example is about an H clock tree in an MCM cir-
cuit of g 3 m technique to offer the clock signal for
four modules located at points r , k , and as
shown in Fig. 3. The H tree is etched on a silicon sub-
strate which is assumed to be the ideal ground. The cir-
cuit is illuminated by a plane EM wave. There are seven
TLs , r , k , r r r k , k and k ,each of them having the same length of
y
cm. The first
three TLs have the PUL parameters y
b b nH/m,
3
b pF/m,
3 3
b /m and
b S/m, and the
other TLs
b bnH/m,
3
y
bpF/m,
b b /m
and
bS/m. At points ,
r and
k , there are three
identical inverters used as buffers to drive the clock sig-
nal.
The applied input is periodic clock signal whose
rise/fall time is b
ps. The illuminating EM wave is
a trapezoidal pulse having rise/fall time of b
ps and
width ofy
ns. The phase of the EM wave is referred
by point at which the delay of EM wave is ns.
As we focus on the effect of the illuminating EM wave
on the integrated circuits, for simplicity we assume that
the EM wave is still the uniform wave in free space at
the top of the circuit. For more accurate modeling the
nonuniformity should be considered due to nonuniform
distribution of media and metals. Using the heuristic,
each of the TLs is modeled by using FDQ with y
(4
PPW) as in Eqn. 15, whose coefficients have been
pre-calculated.
Let the EM wave have the propagation configuration
as!
4 #,
! %
4 #, and
'
b #(refer to Fig. 1).
The responses are shown in Fig. 3.
Fig. 3 shows that, without EM wave interference, the
waveforms at the leaf points
r
t
are identical. With
the EM wave coupling in this configuration, the wave-
forms at
r and
are still identical, so are the wave-
forms at k and , but the two sets of clock wave-
forms are severely skewed, due to the effect of the illu-
minating EM waves.
5 CONCLUSIONS
An efficient numerical approximation technique, call
the Finite Difference Quadrature (FDQ) Method, is first
proposed to solve partial differential equations (PDEs),
and has been adapted to model transmission lines (TLs)
with external field coupling. A discrete modeling ap-
proach, the FDQ adapts grid points along the transmis-
sion lines to compute the finite difference between ad-
jacent grid points by estimating a weighted linear sum
of derivatives at a set of points belonging to the do-main. Similar to the Gaussian Quadrature method to
compute the numerical integrals, the FDQ method uses
global quadrature method to construct the approxima-
tion framework, however, to numerically compute fi-
nite differences. As a global approximation technique,
the FDQ needs much sparser grid points than the fi-
nite difference (FD) method does to achieve required
accuracy. Equivalent voltage and current sources are
derived, which excite the TLs at the grid points. Equiv-
alent circuit models are therefore derived to represent
the TLs illuminated by external electromagnetic waves.
A heuristic of FDQ modeling resolution of two differ-
ences per wavelength is given to determine the order in
the application of FDQ modeling. The FDQ method
supplies a general numerical technique that can solve
partial differential equations (PDEs) accurately and ef-
ficiently.
References
[1] C. R. Paul, Analysis of multiconductor transmission
lines. New York, NY: Wiley, 1994.
[2] I. Erdin, M. S. Nakhla, and R. Achar, Circuit anal-
ysis of electromagnetic radiation and field coupling
effects for networks with embedded full-wave mod-ules, IEEE Trans. Electromagnetic Compatibility,
vol. 42, no. 4, pp. 449460, 2000.
[3] M. Omid, Y. Kami, and M. Hayakawa, Field
coupling to nonuniform and uniform transmission
lines, IEEE Trans. Electromagnetic Compatibility,
vol. 39, no. 3, pp. 201211, 1997.
[4] M. N. O. Sadiku, Numerical techniques in electro-
magnetics. Boca Raton, FL: CRC, 2001.