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EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
1
Motivation for CDR: Deserializer (1)
If input data were accompanied by a well-synchronized clock, deserialization
could be done directly.
Input clock
Input data
channel
÷2 ÷2
1:2
DMUX
1:2
DMUX
1:2
DMUX
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
2
• Providing two high-speed channels (for data & clock) is expensive.
• Alignment between data & clock signals can vary due to different channel
characteristics for the different frequency components. Hence retiming
would still be necessary.
Clock
Data
input data Clock
Recovery
circuit
retimed data
recovered clock
PLLs naturally provide synchronization between external and internal timing sources.
A CDR is often implemented as a PLL loop with a special type of PD...
Motivation for CDR (2)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
3
RZ spectrum has energy at 1/Tc conventional phase detector can be used.
f
S
xf( )
1
Tb
Return-to-Zero vs. Non-Return-to-Zero Formats
NRZ
RZ
1 0 1 1 0 1 0
NRZ spectrum has null at 1/Tc ??
Tb
f
2
Tb
3
Tb
2
Tb
S
xf( )
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
4
Phase Detection of RZ Signals
VdataVRCK
Vd
Vdata
VRCK
Vd
• Phase detection operates same as for clock signals for logic 1.
• Vd exhibits 50% duty cycle for logic 0.
• Kpd will be data dependent.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
5
Phase Detection of NRZ Signals
Vdata
VRCK
Vd
Vdata
VRCK
Vd
Since data rate is half the clock rate, multiplying phase detection is ineffective.
• RZ signals can use same phase detector as clock signals
• RZ data path circuitry requires bandwidth that is double that of NRZ.
• Different type of phase detection required for NRZ signals.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
6
Idea: Mix NRZ data with delayed version of itself
instead of with the clock.
Example: 1010 data pattern (differential signaling)
1
2Tb
1
Tb
• • •
• • •
• • •
XX
= =
Tb
3
2Tb
5
2Tb
fundamental generated
2
Tb
1
2Tb
3
2Tb
5
2Tb
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
7
Operation of D Flip-Flips (DFFs)
CMOS transmission gate:
D
CK
CK
CK
CK
QI
latch:
D
CK
CK
CK
CK
QICK
CK CK
CK
Q
Master Slave
DFF:
Ideal waveforms:
D
CK
Q
D0 D1 D2
D0 D1 D2
Symbol:
D Q
No bubble Q changes following rising edge of CK
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
8
DFF Setup & Hold Time
tsetup thold
When a data transition occurs within the setup & hold region, metastability occurs.
D
CK
Q
At CK rising edge, the master latches and the slave drives.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
9
DFF Clock-to-Q Delay
D
CK
CK
CK
CK
QICK
CK CK
CK
Q
Master Slave
D0 D1 D2
D0 D1 D2
D
CK
Q
tck-q
tck-q is determined by delays of tgate and
inverter.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
10
Din
RCK
P
Q
Q
P
D0
D0
D1
D1
D2
D2
D3
D3
D4
D1 D2 D3
D0 D1 D2 D3
D0 D1 D2 D3
D0 D1 D2 D3
D0
D1
D1
D2
D2
D3
D3
D4
Din
RCK
Delay between Din to Q is related to phase between Din & RCK
Realization of Data/Data Mixing :
RCK early: RCK synchronized:
Same as Din,
synchronized with RCK
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
11
Define zero phase difference as a data transition coinciding with RCK falling edge;
i.e., RCK rising edge is in center of data eye.
2
=t
Tb
1
2
Q
P
Din
RCK
RCK early ( < 0): RCK synchronized ( = 0):
Tb
t
Tb
t
t =Tb
2+
1
2
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
12
Din
RCK
P
Q
0101… pattern: 0011… pattern:
Phase detector characteristic also
depends on transition density:
Q
P
Din
RCK
VP =Vswing 2t
Tb
1
VP =Vswing
t
Tb
1
In general,
VP =Vswing 2t
Tb
1
where average transition density
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
13
t
Tb
=2
+1
2
VP
Vswing
= 2t
Tc
1
VP
Vswing
= + ( 1)
- +
VP
Vswing
= 0.25 = 0.5
= 1
Kpd =
= 0VP
Vswing
= 1
Both slope and offset of phase-voltage characteristic
vary with transition density!
Constructing CDR PD Characteristic
slope:
intercept:
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
14
To cancel phase offset:
Din
RCK
P
Q
R
QR
D0 D1 D2 D3
D0 D1 D2 D3
Q
RCK
QR
R
Kpd still varies with ,
but offset variation cancelled.
C. R. Hogge, “A self-correcting clock recovery circuit,”
IEEE J. Lightwave Tech., vol. 3, pp. 1312-1314, Dec.
1985.
Always 50% duty cycle;
average value is ( 1) Vswing
-+
VP VR
Vswing
+1
-1
= 1
= 0.5
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
15
Transconductance Block
ISS ISS
P+ P- R- R+
Iout+ Iout-
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
16
Due to inherent mixing operation, Hogge PD is not a good frequency
detector. A frequency acquisition loop with a reference clock is
usually needed:
J. Cao et al., “OC-192 transmitter and receiver in 0.18μ
CMOS,” JSSC. vol. 37, pp. 1768-1780, Dec. 2002.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
17
Non-Idealities in Hogge Phase Detector:
A. Clock-to-Q Delay (1)
Din
RCK
P
Q
R
QR
Din
RCK
Q
QR
P
R
tck-Q
tck-Q
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
18
Din
RCK
Q
QR
P
R
tck-Q
tck-Q
VP VR
Vswing
+
-os
os
= 2tck Q
Tc
Non-Idealities in Hogge Phase Detector:
A. Clock-to-Q Delay (2)
Result is an input-referred phase offset:
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
19
Din
RCK
tck-Q
CDRDin
Dout
RCK
Phase offset moves RCK away from
center of data, making retiming less
robust.
Non-Idealities in Hogge Phase Detector:
A. Clock-to-Q Delay (3)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
20
Non-Idealities in Hogge Phase Detector:
A. Clock-to-Q Delay (4)
Din
RCK
P
Q
R
QR
tck-Q
tck-Q
t
Set t t
CK Q
D t
Din
D t
RCK
Q
QR
P
R
Use a compensating delay:
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
21
Non-Idealities in Hogge Phase Detector:
B. Delay Between P & R (1)
Din
RCK
P
Q
R
QR
Din
RCK
Q
QR
P
R
P and R are offset by 1/2 clock period
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
22
P
R
Din
RCK
P
Q
R
QR
Vcontrol
to VCO
Non-Idealities in Hogge Phase Detector:
B. Delay Between P & R (2)
Average value of Vcontrol is
well-controlled, but resulting ripple
causes high-frequency jitter.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
23
Idea: Based on R output,
create compensating pulses:
Din
RCK
P
R
P
R
DFF
latch
latch
latch
Din
RCK
Q
QR
P (up)
R (dn)
Vcontrol
Standard Hogge/charge pump
operation for single input pulse:
Non-Idealities in Hogge Phase Detector:
B. Delay Between P & R (3)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
24
Din
RCK
P
R
P
R
DFF
latch
latch
latchQ4
Q3
Q2
Q1
Din
RCK
Q4
Q3
Q2
Q1
Vcontrol
P (up)
R (dn)
P’(dn)
R’(up)
Cancels out effect of next pulse
Non-Idealities in Hogge Phase Detector:
B. Delay Between P & R (4)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
25
Other Nonidealities of Hogge PD (1)
PD
Dif
fere
nti
al
Ou
tpu
t (m
V)
0
-20
-40
-60
60
40
20
0 10p 20p 30p 40p 50p-30p-40p-50p
-20p -10p
Data Delay in regard to Clock (s)
response from
ideal linear PD
simulated result
of one linear PD
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
26
Effect of Transition Density:
Other Nonidealities of Hogge PD (2)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
27
Effect of DFF bandwidth limitation:
Other Nonidealities of Hogge PD (3)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
28
Effect of XOR bandwidth limitation:
Since the PD output signals are averaged, XOR bandwidth limitation has negligible effect.
Other Nonidealities of Hogge PD (4)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
29
Effect of XOR Asymmetry:
Other Nonidealities of Hogge PD (5)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
30
Binary Phase Detectors
Idea: Directly observe phase alignment between clock & data
Clock falling edge early:
Decrease Vcontrol
Clock falling edge late:
Increase Vcontrol
Clock falling edge centered:
No change to Vcontrol
Ideal binary
phase-voltage characteristic: +1
-1
VP
Vswing
Also known as
“bang-bang” phase detector
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
31
D Flip-Flop as Phase Detector
Early clock:
Data transitions align
with clock low
Late clock:
Data transitions align
with clock high
Din
RCK
Din
RCK
RCK
D
in
VP
VPRCK
D
in
D
in
D
in
=
Realization using double-clocked DFF; note
that RCK/Din connections are reversed:
Top (bottom) DFF detects on Din rising (falling)
edge; DFF selected by opposite Din edge to
avoid false transitions due to clock-q delay.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
32
What happens if =0?
tsetup
thold
D
CK
Q
• If transition at D input occurs within
setup/hold time, metastable operation
results.
• Q output can “hang’’ for an arbitrarily
long time if zero crossings of D & CK
occur sufficiently close together.
• Metastable operation is normally
avoided in digital circuit operation(!)
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
33
Dog Dish Analogy
???
A dog placed equidistant between two dog dishes will starve (in theory).
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
34
Non-Idealities in Binary DFF Phase Detector
1. Metastable operation difficult to characterize & simulate, varies widely
over processing/temperature variations. Kpd (and therefore jitter transfer
function parameters) are difficult to analyze. Exact value of Kpd depends
on metastable behavior and varies with input jitter.
2. Large-amplitude pattern-dependent variation is present in phase detector
output while locked.
3. During long runs phase detector output remains latched, resulting in VCO
frequency changing continuously:
VP
RCK
D
in
fvco
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
35
Idea: Change VCO frequency for only one clock period
VP
RCK
D
in
RCK early RCK late
Circuit realization should sample data with clock (instead of clock with data)
while maintaining bang-bang operation.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
36
Alexander Phase Detector
RCK
D
in
Q1Q2
Q3 Q4
UP
DN
Din
RCK
Q1
Q2
Q3
Q4
UP
DN
RCK early
Q1 leads Q3; Q2/Q4 in phase
RCK late
Q3 leads Q1; Q1/Q4 in phase
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
37
Simulation Results: Alexander PD
DFF outputs
VCO control
voltage
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
38
Binary PDLinear PD
Simulation Comparison:
Linear vs. Binary
• very small freq. acquisition range
• low steady-state jitter
• high freq. acquisition range
• high steady-state jitter
Vcontrol Vcontrol
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
39
Half-Rate CDRs
To relax speed requirements for a given fabrication technology, a half-
rate clock signal can be recovered:
Din
RCK
RCK2
input data
full-rate recovered clock
half-rate recovered clock
• Can be used in in applications (e.g., deserializer) where full-rate clock is
not required.
• Duty-cycle distortion will degrade bit-error ratio & jitter tolerance
compared to full-rate versions.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
40
Idea 1: Input data can be immediately
demultiplexed with half-rate clock
Din
RCK2
DA
DB
Din
RCK2
DA
DB
D0 D1 D2 D3 D4
D0 D2 D4
D1 D3
synchronized with
clock transitions
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
41
Din
RCK2latch latch
latch latch
DAXA
XB DB
DB
RCK2
Din
XA
XB
DA
Splitting D flip-flops
into individual latches:
synchronized with
RCK2
synchronized with
both RCK2 & Din
These pulse widths
contain phase information.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
42
DB
RCK2
Din
XA
XB
DA
P = X
AX
B
R = D
AD
B
RCK2
Din
P R
XA
XB
DA
DB
1
2
Complete Linear Half-Rate PD
J. Savoj & B. Razavi, “A 10Gb/s CMOS
clock and data recovery circuit with a
half-rate linear phase detector,”
JSSC, vol. 36, pp. 761-768, May 2001.
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
43
Idea 2: Observe timing between Din, RCK and quadrature RCKQ
Din
RCK
RCKQ
Din
RCK
RCKQ
S0 S1 S2 S0 S1 S2
Clock early Clock late
S0, S2 sampled with RCK transitions
S1 sampled with RCKQ transitions
Phase logic:
S
0S
1= 0( ) and S
1S
2= 1( )
S
0S
1= 1( ) and S
1S
2= 0( )
S
0S
1= 0( ) and S
1S
2= 0( )
clock early
clock late
no transition
EECS 270C
Spring 2008
Prof. Michael Green
Univ. of California, Irvine
44
Din
RCK
RCKQ
DI
DQ
VPD
Din
RCK
RCKQ
DI
DQ
VPD
Din
RCK
RCKQ
DI
DQ
VPD
Clock early Clock late
J. Savoj & B. Razavi, “A 10-Gb/s
CMOS clock and data recovery
circuit with a half-rate binary
phase detector,” JSSC, vol. 38,
pp. 13-21, Jan. 2003.