Dual rail to rail op-amp

7/26/2019 Dual rail to rail op-amp

1/161

LT1632/LT1633

sn1632 16323fs

45MHz, 45V/s, Dual/QuadRail-to-Rail Input and Output

Precision Op Amps

FEATURES

Gain-Bandwidth Product: 45MHz Slew Rate: 45V/s Low Supply Current per Amplifier: 4.3mA Input Common Mode Range Includes Both Rails Output Swings Rail-to-Rail Input Offset Voltage, Rail-to-Rail: 1350V Max Input Offset Current: 440nA Max Input Bias Current: 2.2A Max Open-Loop Gain: 800V/mV Min Low Input Noise Voltage: 12nV/Hz Typ Low Distortion: 92dBc at 100kHz Wide Supply Range: 2.7V to 15V Large Output Drive Current: 35mA Min Dual in 8-Pin PDIP and SO Packages

The LT1632/LT1633 are dual/quad, rail-to-rail input andoutput op amps with a 45MHz gain-bandwidth product anda 45V/s slew rate.

The LT1632/LT1633 have excellent DC precision over thefull range of operation. Input offset voltage is typically lessthan 400V and the minimum open-loop gain of 0.8million into a 10k load virtually eliminates all gain error.Common mode rejection is typically 83dB over the full rail-

to-rail input range when on a single 5V supply for excellentnoninverting performance.

The LT1632/LT1633 maintain their performance for sup-plies from 2.7V to 36V and are specified at 3V, 5V and 15Vsupplies. The inputs can be driven beyond the supplieswithout damage or phase reversal of the output. Theoutput delivers load currents in excess of 35mA.

The LT1632 is available in 8-pin PDIP and SO packageswith the standard dual op amp pinout. The LT1633 featuresthe standard quad op amp configuration and is available in

a 14-pin plastic SO package. These devices can be used asplug-in replacements for many standard op amps toimprove input/output range and performance.

DESCRIPTIONU

APPLICATIONSU

Active Filters Rail-to-Rail Buffer Amplifiers Driving A/D Converters Low Voltage Signal Processing Battery-Powered Systems

, LTC and LT are registered trademarks of Linear Technology Corporation.

FREQUENCY (Hz)

VOLTAGEGAIN(dB)

50

40

30

20

10

0

10

20

30

40

50

60

70100 10k 100k 10M

1632/33 TA02

1k 1M

COMMON MODE INPUT

DIFFERENTIAL INPUT

VS= 3VAV= 100

TYPICAL APPLICATIONU

Single Supply, 40dB Gain, 550kHz Instrumentation Amplifier

+

1/2 LT1632

VIN

VIN+

VOUT

1630/31 F02

R120k

R2

2k

R4

20k

R5

432

R32k

+

1/2 LT1632

3V

Frequency Response


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LT1632/LT1633

sn1632 16323fs

ABSOLUTE MAXIMUMRATINGSW WW U

Total Supply Voltage (V +to V ) ............................. 36VInput Current ..................................................... 10mAOutput Short-Circuit Duration (Note 2) ........ Continuous

Operating Temperature Range ................ 40C to 85C

Specified Temperature Range (Note 4) ..... 40C to 85CJunction Temperature .......................................... 150CStorage Temperature Range ................. 65C to 150CLead Temperature (Soldering, 10 sec).................. 300C

Consult factory for Military and Industrial grade parts.

PACKAGE/ORDER INFORMATIONW UU

ORDER PARTNUMBER

LT1632CN8LT1632CS8LT1632IN8LT1632IS8

ORDER PARTNUMBER

TJMAX= 150C, JA= 150C/ W

TJMAX= 150C, JA= 130C/ W (N8)TJMAX= 150C, JA= 190C/W (S8)

LT1633CSLT1633IS

S8 PART MARKING

1

2

3

4

8

7

6

5

TOP VIEW

OUT A

IN A

+IN A

V

V+

OUT B

IN B

+IN B

S8 PACKAGE8-LEAD PLASTIC SO

N8 PACKAGE8-LEAD PDIP

A

B

16321632I

TOP VIEW

S PACKAGE14-LEAD PLASTIC SO

1

2

3

4

5

67

14

13

12

11

10

98

OUTA

IN A

+IN A

V+

+IN B

IN BOUT B

OUT D

IN D

+IN D

V

+IN C

IN COUT C

A D

B C

ELECTRICAL CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VOS Input Offset Voltage VCM= V+ 400 1350 VVCM= V

400 1350 V

VOS Input Offset Shift VCM= Vto V+ 350 1500 V

Input Offset Voltage Match (Channel-to-Channel) VCM= V, V+(Note 5) 500 2300 V

IB Input Bias Current VCM= V+ 0 1.15 2.2 A

VCM= V 2.2 1.15 0 A

IB Input Bias Current Shift VCM= Vto V+ 2.3 4.4 A

Input Bias Current Match (Channel-to-Channel) VCM= V+(Note 5) 50 880 nA

VCM= V (Note 5) 50 880 nA

IOS Input Offset Current VCM= V+ 40 440 nA

VCM= V 40 440 nA

IOS Input Offset Current Shift VCM= V

to V+

80 880 nAInput Noise Voltage 0.1Hz to 10Hz 400 nVP-P

en Input Noise Voltage Density f = 1kHz 12 nV/ Hz

in Input Noise Current Density f = 1kHz 1.6 pA/ Hz

CIN Input Capacitance 5 pF

AVOL Large-Signal Voltage Gain VS= 5V, VO= 300mV to 4.7V, RL= 10k 450 2000 V/mVVS= 3V, VO= 300mV to 2.7V, RL= 10k 350 1500 V/mV

CMRR Common Mode Rejection Ratio VS= 5V, VCM= Vto V+ 70 83 dB

VS= 3V, VCM= Vto V+ 66 81 dB

TA= 25C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted.

(Note 1)


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LT1632/LT1633

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TA= 25C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted.


CMRR Match (Channel-to-Channel) (Note 5) VS= 5V, VCM= Vto V+ 65 85 dB

VS= 3V, VCM= Vto V+ 61 82 dBPSRR Power Supply Rejection Ratio VS= 2.7V to 12V, VCM= VO= 0.5V 82 100 dB

PSRR Match (Channel-to-Channel) (Note 5) VS= 2.7V to 12V, VCM= VO= 0.5V 79 101 dB

Minimum Supply Voltage (Note 9) VCM= VO= 0.5V 2.6 2.7 V

VOL Output Voltage Swing Low (Note 6) No Load 15 30 mVISINK= 0.5mA 32 60 mVISINK= 25mA, VS= 5V 600 1200 mVISINK= 20mA, VS= 3V 500 1000 mV

VOH Output Voltage Swing High (Note 6) No Load 16 40 mVISOURCE= 0.5mA 42 80 mVISOURCE= 20mA, VS= 5V 910 1800 mVISOURCE= 15mA, VS= 3V 680 1400 mV

ISC Short-Circuit Current VS= 5V 20 40 mAVS= 3V 15 30 mA

IS Supply Current per Amplifier 4.3 5.2 mA

GBW Gain-Bandwidth Product (Note 7) f = 100kHz 22 45 MHz

SR Slew Rate (Note 8) VS= 5V, AV= 1, RL= Open, VO= 4V 13 27 V/sVS= 3V, AV= 1, RL= Open 11 22 V/s

tS Settling Time VS= 5V, AV= 1, RL= 1k, 400 ns0.01%, VSTEP= 2V


VOS Input Offset Voltage VCM= V+ 0.1V 600 2000 V

VCM= V+ 0.2V 600 2000 V

VOSTC Input Offset Voltage Drift (Note 3) 8 15 V/CVCM= V

+ 0.1V 2.5 7 V/C

VOS Input Offset Voltage Shift VCM= V+ 0.2V to V+ 0.1V 400 2300 V

Input Offset Voltage Match (Channel-to-Channel) VCM= V+ 0.2V, V

+ 0.1V (Note 5) 700 3750 V

IB Input Bias Current VCM= V+ 0.1V 0 1.3 2.6 A

VCM= V + 0.2V 2.6 1.3 0 A

IB Input Bias Current Shift VCM= V+ 0.2V to V+ 0.1V 2.6 5.2 A

Input Bias Current Match (Channel-to-Channel) VCM= V+ 0.1V (Note 5) 50 1040 nA

VCM= V + 0.2V (Note 5) 50 1040 nA

IOS Input Offset Current VCM= V+ 0.1V 40 520 nA

VCM= V + 0.2V 40 520 nA

IOS Input Offset Current Shift VCM= V + 0.2V to V+ 0.1V 80 1040 nA

AVOL Large-Signal Voltage Gain VS= 5V, VO= 300mV to 4.7V, RL= 10k 300 1100 V/mV

VS= 3V, VO= 300mV to 2.7V, RL= 10k 200 1000 V/mV

CMRR Common Mode Rejection Ratio VS= 5V, VCM= V+ 0.2V to V+ 0.1V 67 81 dB

VS= 3V, VCM= V+ 0.2V to V+ 0.1V 61 77 dB

CMRR Match (Channel-to-Channel) (Note 5) VS= 5V, VCM= V+ 0.2V to V

+ 0.1V 62 78 dBVS= 3V, VCM= V

+ 0.2V to V

+ 0.1V 57 73 dB

PSRR Power Supply Rejection Ratio VS= 3V to 12V, VCM= VO= 0.5V 81 94 dB

PSRR Match (Channel-to-Channel) (Note 5) VS= 3V to 12V, VCM= VO= 0.5V 77 95 dB

0C < TA< 70C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted.


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LT1632/LT1633

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VCM= V+ 0.2V 700 2400 V

VOSTC Input Offset Voltage Drift (Note 3) 8 15 V/CVCM= V

+ 0.1V 2.5 7 V/C



+(Note 5) 750 4000 V

IB

Input Bias Current VCM

= V+ 0.1V 0 1.46 3.0

AVCM= V

+ 0.2V 3.0 1.46 0 A



VCM= V+ 0.2V (Note 5) 70 1160 nA


VCM= V+ 0.2V 75 580 nA

IOS Input Offset Current Shift VCM= V+ 0.2V to V+ 0.1V 50 1160 nA

AVOL Large-Signal Voltage Gain VS= 5V, VO= 300mV to 4.7V, RL= 10k 250 1000 V/mVVS= 3V, VO= 300mV to 2.7V, RL= 10k 200 800 V/mV

CMRR Common Mode Rejection Ratio VS= 5V, VCM= V+ 0.2V to V+ 0.1V 65 80 dB

VS= 3V, VCM= V+ 0.2V to V+ 0.1V 60 75 dB

CMRR Match (Channel-to-Channel) (Note 5) VS= 5V, VCM= V+ 0.2V to V+ 0.1V 62 78 dBVS= 3V, VCM= V

+ 0.2V to V+ 0.1V 57 73 dB

PSRR Power Supply Rejection Ratio VS= 3V to 12V, VCM= VO= 0.5V 79 95 dB

PSRR Match (Channel-to-Channel) (Note 5) VS= 3V to 12V, VCM= VO= 0.5V 75 95 dB


VOL Output Voltage Swing Low (Note 6) No Load 19 40 mVISINK= 0.5mA 39 80 mVISINK= 25mA, VS= 5V 730 1500 mVISINK= 20mV, VS= 3V 580 1200 mV



VOL Output Voltage Swing Low (Note 6) No Load 18 40 mVISINK= 0.5mA 37 80 mVISINK= 25mA, VS= 5V 700 1400 mVISINK= 20mA, VS= 3V 560 1200 mV

VOH Output Voltage Swing High (Note 6) No Load 16 40 mVISOURCE= 0.5mA 50 100 mVISOURCE= 15mA, VS= 5V 820 1600 mVISOURCE= 10mA, VS= 3V 550 1100 mV





40C < TA< 85C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted. (Note 4)

0C < TA< 70C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted.


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LT1632/LT1633

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40C < TA< 85C, VS= 5V, 0V; VS= 3V, 0V; VCM= VOUT= half supply, unless otherwise noted. (Note 4)

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITSVOS Input Offset Voltage VCM= V

+ 500 2200 VVCM= V

500 2200 V

VOS Input Offset Voltage Shift VCM= Vto V+ 360 2200 V

Input Offset Voltage Match (Channel-to-Channel) VCM= V, V+(Note 5) 700 3500 V

IB Input Bias Current VCM= V+ 0 1.15 2.2 A

VCM= V 2.2 1.15 0 A

IB Input Bias Current Shift VCM= Vto V+ 2.3 4.4 A

Input Bias Current Match (Channel-to-Channel) VCM= V+(Note 5) 50 880 nA

VCM= V (Note 5) 50 880 nA

IOS Input Offset Current VCM= V+ 50 440 nA

VCM= V 50 440 nA

IOS Input Offset Current Shift VCM= Vto V+ 36 880 nA

Input Noise Voltage 0.1Hz to 10Hz 400 nVP-P

en Input Noise Voltage Density f = 1kHz 12 nV/ Hz

in Input Noise Current Density f = 1kHz 1.6 pA/ Hz

CIN Input Capacitance f = 100kHz 3 pF

AVOL Large-Signal Voltage Gain VO= 14.5V to 14.5V, RL= 10k 800 5000 V/mV

VO= 10V to 10V, RL= 2k 400 2500 V/mV

Channel Separation VO= 10V to 10V, RL= 2k 110 127 dB

CMRR Common Mode Rejection Ratio VCM= Vto V + 82 98 dB

CMRR Match (Channel-to-Channel) (Note 5) VCM= Vto V + 80 101 dB

PSRR Power Supply Rejection Ratio VS= 5V to 15V 82 96 dB

PSRR Match (Channel-to-Channel) (Note 5) VS= 5V to 15V 80 101 dB

VOL Output Voltage Swing Low (Note 6) No Load 16 35 mVISINK= 5mA 150 300 mV

ISINK= 25mA 600 1200 mV

VOH Output Voltage Swing High (Note 6) No Load 16 40 mVISOURCE= 5mA 250 500 mVISOURCE = 25mA 1200 2400 mV


VOH Output Voltage Swing High (Note 6) No Load 16 40 mV

ISOURCE= 0.5mA 55 110 mVISOURCE= 15mA, VS= 5V 860 1700 mVISOURCE= 10mA, VS= 3V 580 1200 mV





TA= 25C, VS= 15V, VCM= 0V, VOUT= 0V, unless otherwise noted.


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LT1632/LT1633

sn1632 16323fs

ELECTRICAL CHARACTERISTICSTA= 25C, VS= 15V, VCM= 0V, VOUT= 0V, unless otherwise noted.


ISC Short-Circuit Current 35 70 mA

IS Supply Current per Amplifier 4.6 6 mA


SR Slew Rate AV= 1, RL= Open, VO= 10V, 22 45 V/sMeasure at VO= 5V

tS Settling Time 0.01%, VSTEP= 10V, AV= 1, RL= 1k 575 ns



VCM= V+ 0.2V 800 2750 V

VOSTC Input Offset Voltage Drift (Note 3) 10 17 V/C

VCM= V+

0.1V 5 11 V/CVOS Input Offset Voltage Shift VCM= V+ 0.2V to V+ 0.1V 500 2500 V


+ 0.1V (Note 5) 800 4000 V


VCM= V+ 0.2V 2.6 1.3 0 A



VCM= V + 0.2V (Note 5) 70 1040 nA


VCM= V + 0.2V 70 520 nA


AVOL

Large-Signal Voltage Gain VO= 14.5V to 14.5V, R

L= 10k 600 4000 V/mV

VO= 10V to 10V, RL= 2k 300 2000 V/mV


CMRR Common Mode Rejection Ratio VCM= V+ 0.2V to V+ 0.1V 81 96 dB

CMRR Match (Channel-to-Channel)(Note 5) VCM= V+ 0.2V to V

+ 0.1V 77 95 dB




ISINK= 25mA 680 1400 mV

VOH Output Voltage Swing High (Note 6) No Load 15 40 mVISOURCE= 5mA 300 600 mV

ISOURCE= 25mA 1400 2800 mVISC Short-Circuit Current 28 57 mA



SR Slew Rate AV= 1, RL= Open, VO= 10V, 21 43 V/sMeasured at VO= 5V

0C < TA< 70C, VS= 15V, VCM= 0V, VOUT= 0V, unless otherwise noted.


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ELECTRICAL CHARACTERISTICS40C < TA< 85C, VS= 15V, VCM= 0V, VOUT= 0V, unless otherwise noted. (Note 4)



VCM= V+ 0.2V 1000 3000 VVOSTC Input Offset Voltage Drift (Note 3) 10 17 V/C

VCM= V+ 0.1V 5 11 V/C



+ 0.1V(Note 5) 850 4000 V


VCM= V+ 0.2V 2.8 1.4 0 A



VCM= V+ 0.2V (Note 5) 75 1120 nA


VCM= V + 0.2V 60 560 nA


AVOL Large-Signal Voltage Gain VO= 14.5V to 14.5V, RL= 10k 500 5000 V/mVVO= 10V to 10V, RL= 2k 250 1800 V/mV


CMRR Common Mode Rejection Ratio VCM= V+ 0.2V to V+ 0.1V 81 96 dB

CMRR Match (Channel-to-Channel)(Note 5) VCM= V+ 0.2V to V

+ 0.1V 77 95 dB




ISINK= 25mA 700 1400 mV

VOH Output Voltage Swing High (Note 6) No Load 16 40 mVISOURCE= 5mA 300 600 mVISOURCE= 25mA 1500 3000 mV

ISC Short-Circuit Current 27 54 mA

IS Supply Current per Amplifier 5.3 7 mA


SR Slew Rate AV= 1, RL= Open, VO= 10V, 18 35 V/sMeasure at VO= 5V

Note 5:Matching parameters are the difference between amplifiers A and

D and between B and C on the LT1633; between the two amplifiers on theLT1632.

Note 6:Output voltage swings are measured between the output andpower supply rails.

Note 7:VS= 3V, VS= 15V GBW limit guaranteed by correlation to5V tests.

Note 8:VS= 3V, VS= 5V slew rate limit guaranteed by correlation to15V tests.Note 9:Minimum supply voltage is guaranteed by testing the change ofVOSto be less than 250V when the supply voltage is varied from 3V to2.7V.

The denotes specifications that apply over the full operating temperaturerange.

Note 1: Absolute Maximum Ratings are those values beyond which the life

of a device may be impaired.Note 2:A heat sink may be required to keep the junction temperaturebelow the absolute maximum rating when the output is shortedindefinitely.

Note 3:This parameter is not 100% tested.

Note 4:The LT1632C/LT1633C are guaranteed to meet specifiedperformance from 0C to 70C and are designed, characterized andexpected to meet these extended temperature limits, but are not tested at 40C and 85C. Guaranteed I grade parts are available, consult factory.


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LT1632/LT1633

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TYPICAL PERFORMANCE CHARACTERISTICSUW

Supply Current vs Supply Voltage

TOTAL SUPPLY VOTAGE (V)

0 4

SUPPLYCURRENTPERAMPLIFIER(mA)

36

1630/31 G01

8 12 16 20 24 28 32

6.0

5.5

5.0

4.5

4.0

3.5

3.0

2.5

2.0

TA= 125C

TA= 55C

TA= 25C

TEMPERATURE (C)

50

INPUTBIASCURRENT(A)

2.8

2.0

1.2

0.4

0

0.4

1.2

2.0

2.870

1632/33 G04

20 10 4035 855 25 55 100

VS= 5V, 0VVCM= 0V

VS= 15VVCM= 15V

NPN ACTIVE

PNP ACTIVE

VS= 15VVCM= 15V

VS= 5V, 0VVCM= 5V

TEMPERATURE (C)

75

SUPPLYCURRENTPERAMPLIFIER(mA)

0

1632/33 G02

50 25 25

6.0

5.5

5.0

4.5

4.0

3.5

3.0

2.550 75 125100

VS= 15V

VS= 5V, 0V

Supply Current vs Temperature

Input Bias Current vs Temperature

LOAD CURRENT (mA)

SATURATIONVOL

TAGE(V)

0.01 1 10 100

1632/33 G05

0.1

10

1

0.1

0.01

VS= 5V, 0V

TA= 55C

TA= 125C

TA= 25C

Output Saturation Voltage vs LoadCurrent (Output Low)

LOAD CURRENT (mA)

SATURATIONVOL

TAGE(V)

0.01 1 10 100

1632/33 G06

0.1

10

1

0.1

0.01

VS= 5V, 0V

TA= 55C

TA= 125C

TA= 25C

Output Saturation Voltage vs LoadCurrent (Output High)

COMMON MODE VOLTAGE (V)

2

INPUTBIASCURRENT(A)

2 3 4 5 6

1632/33 G03

1 0 1

2.0

1.5

1.0

0.5

0

0.5

1.0

1.5

2.0

TA= 125C

TA= 55C

TA= 25C

VS= 5V, 0V

Input Bias Current vsCommon Mode Voltage

VOSDistribution, VCM= 0V(PNP Stage)

VOSDistribution, VCM= 5V(NPN Stage)

INPUT OFFSET VOLTAGE (V)

1250

PERCENTOFUNITS(%)

50

40

30

20

10

0750

1632/33 G31

750 250 250 1250

VS= 5V, 0VVCM= 0V


1250

PERCENTOFUNITS(%)

50

40

30

20

10

0750

1632/33 G32

750 250 250 1250

VS= 5V, 0VVCM= 5V


1250

PERCENTOFUNITS(%)

50

40

30

20

10

0750

1632/33 G33

750 250 250 1250

VS= 5V, 0V

VOSShift for VCM= 0V to 5V


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TOTAL SUPPLY VOLTAGE (V)

10

CHANGEINOFFSETVOLTAGE(V)

100

200

300

400

2 3 4 5

1632/33 G07

500

600

TA= 125C TA= 55C

TA= 25C

FREQUENCY (Hz)

1

NOISEVOLTAGE(nV/Hz)

10 100 1000

11632/33 G09

70

60

50

40

30

20

10

0

VS= 5V, 0V

VCM= 2.5VPNP ACTIVE

VCM= 4.25VNPN ACTIVE

Noise Voltage SpectrumMinimum Supply Voltage

0.1Hz to 10HzOutput Voltage Noise

Gain Bandwidth and PhaseMargin vs Supply Voltage


0

GAINBANDWIDTH(MHz) PH

ASEMARGIN(DEG)

5 10 15 20

1632/33 G14

25

120

105

90

75

60

45

30

15

0

80

70

60

50

40

30

20

10

030

PHASE MARGIN

VCM= VS/2

GAIN BANDWIDTH

Gain and Phase vs Frequency

FREQUENCY (Hz)

40

COMMONMODEREJEC

TIONRATIO(dB)

60

80

70

100

120

30

50

90

110

1k 100k 1M 10M

1632/33 G12

2010k

VS= 15V

VS= 5V, 0V

CMRR vs Frequency PSRR vs Frequency

FREQUENCY (Hz)

POWERSUPPLYREJEC

TIONRATIO(dB)

100

90

80

70

60

50

40

30

20

10

01k 100k 1M 10M

1632/33 G13

10k

VS= 15V

POSITIVE SUPPLY

NEGATIVE SUPPLY

Channel Separation vs Frequency

FREQUENCY (Hz)

10

CHANNELSEPARATION(dB)

100 1k 10k 100k 1M

1632/33 G15

40

50

60

70

80

90

100

110

120

130

140

VS= 15VVOUT= 10VP-PRL= 2k

Noise Current Spectrum

FREQUENCY (Hz)

1

8

CURRENTNOISE(pA/Hz)

10

12

14

16

10 100 1000

1632/33 G10

6

4

2

0

18

20

VS= 5V, 0V

VCM= 2.5VPNP ACTIVE

VCM= 4.25VNPN ACTIVE

FREQUENCY (MHz)

VOLTAGEGAIN(dB) PH

ASE

SHIFT

(DEG)

80

70

60

50

40

30

20

10

010

20

225

180

135

90

45

0

45

90

135180

2250.01 1 10 100

1632/33 G11

0.1

PHASE

GAIN

RL= 1kVS= 3V, 0VVS= 15V

TIME (1SEC/DIV)

O

UTPUTVOLTAGE(200nV/DIV)

1632/33 G08

VS= 5V, 0VVCM= VS/2


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Output Step vsSettling Time to 0.01%

SETTLING TIME (s)0 0.25

10

OUTPUTSTEP(V)

8

4

2

0

10

4

0.50 0.75 1.00

1632/33 G18

6

6

8

2

VS= 15V

NONINVERTING INVERTING

INVERTINGNONINVERTING

CAPACITIVE LOAD (pF)

1

OVERSHOOT(%)

10 100 1000

1632/33 G16

90

80

70

60

50

40

30

VS= 5V, 0VAV= 1RL= 1k

Capacitive Load Handling

OUTPUT VOLTAGE (V)

5 4 3 2 1

INPUTVOLTAGE(V)

200

150

100

50

0

50

100

150

2003

1632/33 G21

10 2 4 65 7

VS= 15VRL= 100

OUTPUT VOLTAGE (V)

0

INPUTVOLTAGE(V)

3 5

1632/33 G20

1 2 4

20

15

10

5

0

5

10

15

206

VS= 5V, 0V

RL= 1k

RL= 10k

Open-Loop Gain Open-Loop Gain Open-Loop Gain

OUTPUT VOLTAGE (V)

20 15

INPUTVOLTAGE(V)

0

10

20

1632/33 G19

10

2010 5 0 5 10 15

20

5

5

15

15VS= 15V

RL= 1k

RL= 10k

TIME AFTER POWER-UP (SEC)

0

CHANGEINOFFSETVO

LTAGE(V)

100

0

100

200

300

400

50060 100 160

1632/33 G22

20 40 80 120 140

N8 PACKAGE, VS= 5V, 0V

S8 PACKAGE, VS= 5V, 0V

N8 PACKAGE, VS= 15V

LT1633CS, VS= 5V, 0V

S8 PACKAGE, VS= 15V

LT1633CS, VS= 15V

FREQUENCY (kHz)

THD+NOISE(%)

1

0.1

0.01

0.001

0.00010.1 10 100

1632/33 G23

1

VS= 3V, 0VAV= 1

VIN= 2VP-PRL= 10k

VS= 5V, 0VAV= 1

VS= 5V, 0V AND 3V, 0VAV= 1

Total Harmonic Distortion + Noisevs Frequency


0

SLEW

RATE(V/s)

8 12 20 28 324 16 24 36

1632/33 G17

55

50

45

40

35

30

25

20

RISING EDGE

FALLING EDGE

VOUT= 80% OF VSAV= 1

Slew Rate vs Supply Voltage

FREQUENCY (kHz)

1

OUTPUTVOLTAGESW

ING(VP-P)

10 100 1000

1630/31 G24

5

4

3

2

1

0

AV= 1

VS= 5V, 0V

AV= 1

Maximum Undistorted OutputSignal vs FrequencyWarm-Up Drift vs Time


11/1611

LT1632/LT1633

sn1632 16323fs


5V Large-Signal Response

1632/33 G26VS= 5V, 0VAV= 1RL= 1k

5V Small-Signal Response

163233 G25VS= 5V, 0VAV= 1RL= 1k

Harmonic Distortion vs Frequency

FREQUENCY (kHz)

100

HARMONICDISTORTION(dBc)

0

20

40

60

80

1001000 2000

1632/33 G29

200 500

VS= 5V, 0V

AV= 1VIN= 2VP-PRL= 150RL= 1k

2ND

3RD

2ND

3RD

Harmonic Distortion vs Frequency 15V Large-Signal Response

1632/33 G27

VS= 15V

AV= 1RL= 1k

15V Small-Signal Response

FREQUENCY (kHz)

100

HARMONICDISTORTION(dBc)

0

20

40

60

80

1001000 2000

1632/33 G301000

200 500

2ND

3RD

3RD

VS= 5V, 0VAV= 1VIN= 2VP-P

RL= 150RL= 1k

2ND

1632/33 G28VS= 15VAV= 1

RL= 1k

APPLICATIONS INFORMATIONWU UU

Rail-to-Rail Input and Output

The LT1632/LT1633 are fully functional for an input andoutput signal range from the negative supply to the posi-tive supply. Figure 1 shows a simplified schematic of the

amplifier. The input stage consists of two differentialamplifiers, a PNP stage Q1/Q2 and an NPN stage Q3/Q4that are active over different ranges of input commonmode voltage. The PNP differential input pair is active forinput common mode voltages VCMbetween the negativesupply to approximately 1.5V below the positive supply.As VCM moves closer toward the positive supply, thetransistor Q5 will steer the tail current I1to the currentmirror Q6/Q7, activating the NPN differential pair and the

PNP pair becomes inactive for the rest of the input com-mon mode range up to the positive supply.

The output is configured with a pair of complementarycommon emitter stages Q14/Q15 that enables the output

to swing from rail to rail. These devices are fabricated onLinear Technologys proprietary complementary bipolarprocess to ensure similar DC and AC characteristics.Capacitors C1 and C2 form local feedback loops that lowerthe output impedance at high frequencies.

Power Dissipation

The LT1632/LT1633 amplifiers combine high speed andlarge output current drive in a small package. Because the


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LT1632/LT1633

sn1632 16323fs


amplifiers operate over a very wide supply range, it ispossible to exceed the maximum junction temperature of150C in plastic packages under certain conditions. Junc-tion temperature TJis calculated from the ambient tem-perature TAand power dissipation PDas follows:

LT1632CN8: TJ= TA+ (PD 130C/W)LT1632CS8: TJ= TA+ (PD 190C/W)LT1633CS: TJ= TA+ (PD 150C/W)

The power dissipation in the IC is the function of the supplyvoltage, output voltage and load resistance. For a givensupply voltage, the worst-case power dissipation PDMAXoccurs at the maximum supply current and when theoutput voltage is at half of either supply voltage (or themaximum swing if less than 1/2 supply voltage). There-fore PDMAXis given by:

PDMAX= (VS ISMAX) + (VS/2)2/RL

To ensure that the LT1632/LT1633 are used properly,calculate the worst-case power dissipation, use the ther-mal resistance for a chosen package and its maximumjunction temperature to derive the maximum ambienttemperature.

Example: An LT1632CS8 operating on 15V supplies anddriving a 500, the worst-case power dissipation peramplifier is given by:

PDMAX= (30V 5.6mA) + (15V 7.5V)(7.5/500) = 0.168 + 0.113 = 0.281W

If both amplifiers are loaded simultaneously, then the totalpower dissipation is 0.562W. The SO-8 package has ajunction-to-ambient thermal resistance of 190C/W in stillair. Therefore, the maximum ambient temperature that thepart is allowed to operate is:

TA= TJ (PDMAX 190C/W)TA= 150C (0.562W 190C/W) = 43C

For a higher operating temperature, lower the supplyvoltage or use the DIP package part.

Input Offset Voltage

The offset voltage changes depending upon which inputstage is active, and the maximum offset voltages are

trimmed to less than 1350V. To maintain the precisioncharacteristics of the amplifier, the change of VOSover theentire input common mode range (CMRR) is guaranteedto be less than 1500V on a single 5V supply.

Input Bias Current

The input bias current polarity depends on the inputcommon mode voltage. When the PNP differential pair isactive, the input bias currents flow out of the input pins.

Q4

Q6

VBIASD7D5

+ IN

D2

Q3

Q7

Q1

I1

I2

+

+

Q9

Q2

D4

D1

D3

IN OUT

V

V+

D8D6

Q5

Q12

Q8

Q14

1632/33 F01

C1

R1

R6225

R7225

R3

V CC

R4 R5

C2

R2

Q11 Q13 Q15

BUFFERAND

OUTPUT BIAS

Figure 1. LT1632 Simplified Schematic Diagram


13/1613

LT1632/LT1633

sn1632 16323fs


They flow in the opposite direction when the NPN inputstage is active. The offset voltage error due to input biascurrents can be minimized by equalizing the noninverting

and inverting input source impedance.

Output

The outputs of the LT1632/LT1633 can deliver large loadcurrents; the short-circuit current limit is 70mA. Take careto keep the junction temperature of the IC below theabsolute maximum rating of 150C (refer to the PowerDissipation section). The output of these amplifiers havereverse-biased diodes to each supply. If the output isforced beyond either supply, unlimited current will flow

through these diodes. If the current is transient and limitedto several hundred mA, no damage to the part will occur.

Overdrive Protection

To prevent the output from reversing polarity when theinput voltage exceeds the power supplies, two pairs ofcrossing diodes D1 to D4 are employed. When the inputvoltage exceeds either power supply by approximately700mV, D1/D2 or D3/D4 will turn on, forcing the output tothe proper polarity. For this phase reversal protection towork properly, the input current must be limited to less

than 5mA.If the amplifier is to be severely overdriven, anexternal resistor should be used to limit the overdrivecurrent.

The LT1632/LT1633s input stages are also protectedagainst large differential input voltages by a pair of back-to-back diodes D5/D8. When a differential voltage ofmore than 1.4V is applied to the inputs, these diodes willturn on, preventing the emitter-base breakdown of theinput transistors. The current in D5/D8 should be limited

to less than 10mA. Internal 225resistors R6 and R7 willlimit the input current for differential input signals of 4.5Vor less. For larger input levels, a resistor in series with

either or both inputs should be used to limit the current.Worst-case differential input voltage usually occurs whenthe output is shorted to ground. In addition, the amplifieris protected against ESD strikes up to 3kV on all pins.

Capacitive Load

The LT1632/LT1633 are wideband amplifiers that candrive capacitive loads up to 200pF on 15V supplies in aunity-gain configuration. On a 3V supply, the capacitiveload should be kept to less than 100pF. When there is a

need to drive larger capacitive loads, a resistor of 20to50 should be connected between the output and thecapacitive load. The feedback should still be taken from theoutput so that the resistor isolates the capacitive load toensure stability.

Feedback Components

The low input bias currents of the LT1632/LT1633 make itpossible to use the high value feedback resistors to set thegain. However, care must be taken to ensure that the poleformed by the feedback resistors and the total capacitance

at the inverting input does not degrade stability. Forinstance, the LT1632/LT1633 in a noninverting gain of 2,set with two 20k resistors, will probably oscillate with10pF total input capacitance (5pF input capacitance and5pF board capacitance). The amplifier has a 6MHz cross-ing frequency and a 55phase margin at 6dB of gain. Thefeedback resistors and the total input capacitance form apole at 1.6MHz that induces a phase shift of 75at 5MHz!The solution is simple: either lower the value of theresistors or add a feedback capacitor of 10pF or more.

TYPICAL APPLICATIONSU

Single Supply, 40dB Gain, 550kHz InstrumentationAmplifier

An instrumentation amplifier with a rail-to-rail outputswing, operating from a 3V supply can be constructed withthe LT1632 as shown in the first page of this data sheet.

The amplifier has a nominal gain of 100, which can beadjusted with resistor R5. The DC output level is set by thedifference of the two inputs multiplied by the gain of 100.The voltage gain and the DC output level can beexpressed as follows:


14/1614

LT1632/LT1633

sn1632 16323fs

Figure 4. RF Amplifier Control Biasing and DC Restoration


A R

R

R

R

R R

R

V V V A

V

OUT IN IN V

= + + +

= +

4

31

2

1

3 2

5

Common mode range can be calculated by the followingequations:

Lower

VV

A

R

RV

Upper

VV

A

R

RV V

where V

CMLOUT

V

CMHOUT

VS

S

limit common mode input voltage

limit common mode input voltage

is supply voltage.

=

+

=

+ ( )

2

50 1

1 0

1 1

2

50 15

1 0

1 1

. .

.

. .

.

For example, the common mode range is from 0.15V to2.65V if the output is set at one half of the 3V supply. Thecommon mode rejection is greater than 110dB at 100Hzwhen trimmed with resistor R1. The amplifier has abandwidth of 550kHz.

Single Supply, 400kHz, 4th Order Butterworth Filter

The circuit shown in Figure 2 makes use of the low voltageoperation and the wide bandwidth of the LT1632 to createa 400kHz 4th order lowpass filter with a single supply. Theamplifiers are configured in the inverting mode to mini-mize common mode induced distortion and the outputcan swing rail-to-rail for the maximum dynamic range.Figure 3 displays the frequency response of the filter.Stopband attenuation is greater than 85dB at 10MHz.

+

A11/2 LT1632

VOUT

1632/33 F04

5V

5V

HP-MSA0785HP-MSA0785

R310k

L1220H

C50.01F

L2220H

Q12N3906 Q2

2N3906

C60.01F

R550

R110

R2453

R410

C31500pF

+A2

1/2 LT1632

C41500pF

C21500pF

C10.01F

VIN

L43.9H

L33.9H

+ ++

RF1 RF2

Figure 2. Single Supply, 400kHz, 4th Order Butterworth Filter

FREQUENCY (Hz)

0.1k

GAIN(dB)

1k 10k 100k 1M 10M

1632/33 F03

10

0

10

20

30

40

50

60

70

80

90

VS= 3V, 0VVIN= 2.5VP-P

Figure 3. Frequency Response

+

1/2 LT1632

2.32k

VIN

VS/2

VOUT

1632/33 F02

220pF

2.32k 6.65k

+

1/2 LT1632

2.74k 22pF

470pF

5.62k2.74k

47pF

With a 2.25VP-P, 100kHz input signal on a 3V supply, thefilter has harmonic distortion of less than 87dBc.

RF Amplifier Control Biasing and DC Restoration

Taking advantage of the rail-to-rail input and output, andthe large output current capability of the LT1632, thecircuit shown in Figure 4 provides precise bias current forthe RF amplifiers and restores the DC output level. Toensure optimum performance of an RF amplifier, its biaspoint must be accurate and stable over the operating


15/1615

LT1632/LT1633

sn1632 16323fs

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.

However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-tation that the interconnection of its circuits as described herein will not infringe on existing patent rights.

S Package14-Lead Plastic Small Outline (Narrow 0.150)

(LTC DWG # 05-08-1610)

temperature range. The op amp A1 combined with Q1, Q2,R1, R2 and R3 establishes two current sources of 21.5mAto bias RF1 and RF2 amplifiers. The current of Q1, is

determined by the voltage across R2 over R1, which isthen replicated in Q2. These current sources are stable andprecise over temperature and have a low dissipated power

due to a low voltage drop between their terminals. Theamplifier A2 is used to restore the DC level at the output.With a large output current of the LT1632, the output can

be set at 1.5V DC on 5V supply and 50load. This circuithas a 3dB bandwidth from 2MHz to 2GHz and a powergain of 25dB.


0.016 0.050

0.406 1.270

0.010 0.020

(0.254 0.508)45

0 8TYP

0.008 0.010

(0.203 0.254)

S14 06951 2 3 4

0.150 0.157**

(3.810 3.988)

14 13

0.337 0.344*

(8.560 8.738)

0.228 0.244

(5.791 6.197)

12 11 10 9

5 6 7

80.053 0.069

(1.346 1.752)

0.014 0.019

(0.355 0.483)

0.004 0.010

(0.101 0.254)

0.050

(1.270)TYP

DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASHSHALL NOT EXCEED 0.006" (0.152mm) PER SIDE

DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEADFLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE

*

**

PACKAGE DESCRIPTIONU

Dimensions in inches (millimeters) unless otherwise noted.

N8 Package8-Lead PDIP (Narrow 0.300)

(LTC DWG # 05-08-1510)

N8 1197

0.009 0.015

(0.229 0.381)

0.300 0.325

(7.620 8.255)

0.325+0.0350.015

+0.8890.381

8.255( )0.100 0.010

(2.540 0.254)

0.065

(1.651)

TYP

0.045 0.065(1.143 1.651)

0.130 0.005

(3.302 0.127)

0.020

(0.508)MIN

0.018 0.003

(0.457 0.076)

0.125

(3.175)MIN 1 2 3 4

8 7 6 5

0.255 0.015*

(6.477 0.381)

0.400*

(10.160)MAX

*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)

S8 Package8-Lead Plastic Small Outline (Narrow 0.150)

(LTC DWG # 05-08-1610)

SO8 0996

0.016 0.050

0.406 1.270

0.010 0.020

(0.254 0.508)45

0 8TYP0.008 0.010

(0.203 0.254)

0.053 0.069

(1.346 1.752)

0.014 0.019

(0.355 0.483)

0.004 0.010

(0.101 0.254)

0.050

(1.270)

TYP

1 2 3 4

0.150 0.157**

(3.810 3.988)

8 7 6 5

0.189 0.197*

(4.801 5.004)

0.228 0.244

(5.791 6.197)

DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASHSHALL NOT EXCEED 0.006" (0.152mm) PER SIDE

DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEADFLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE

*

**


16/16

LT1632/LT1633

sn1632 16323fs

LT/TP 0998 4K PRINTED IN USALinear Technology Corporation

TYPICAL APPLICATIONU

+

A21/2 LT1632

VIN

VOUT

1632/33 F05

5V

5V

R21k

R91k

R85k

R1110k

R1010k

R61k

R1500

R51k

R71k

R1.62k

R1.62k

C1000pF

C1000pF

+A1

1/2 LT1632

C24.7F

C54.7F

C12.2F

Figure 5. Tunable Q Notch Filter

PART NUMBER DESCRIPTON COMMENTS

LT1211/LT1212 Dual/Quad 14MHz, 7V/s, Single Supply Precision Op Amps Input Common Mode Includes Ground, 275V VOS(MAX),6V/C Max Drift, Max Supply Current 1.8mA per Op Amp



LT1498/LT1499 Dual/Quad 10MHz, 6V/s Rail-to-Rail Input and Output High DC Accuracy, 475V VOS(MAX), 4V/C Max Drift,

C-LoadTM

Op Amps Max Supply Current 2.2mA per AmpLT1630/LT1631 Dual/Quad 30MHz, 10V/s Rail-to-Rail Input and Output Op Amps High DC Accuracy, 525V VOS(MAX), 70mA Output Current,

Max Supply Current 4.4mA per Amp

C-Load is a trademark of Linear Technology Corporation.

RELATED PARTS

f

RCR k

C pF

V VR

R RV

A

O

O DC

V

=

=

=

=+

=

=

1

21 62

1000

511

11 102 5

2

.

.( )

Tunable Q Notch Filter

A single supply, tunable Q notch filter as shown in Figure5 is built with LT1632 to maximize the output swing. Thefilter has a gain of 2, and the notch frequency (fO) is set bythe values of R and C. The resistors R10 and R11 set up theDC level at the output. The Q factor can be adjusted byvarying the value of R8. The higher value of R8 will

decrease Q as depicted in Figure 6, because the outputinduces less of feedback to amplifier A2. The value of R7should be equal or greater than R9 to prevent oscillation.

If R8 is a short and R9 is larger than R7, then the positivefeedback from the output will create phase inversion at theoutput of amplifier A2, which will lead to oscillation.

FREQUENCY (kHz)

40

20

0

20

40

GAIN(VOUT/V

IN)(dB)

13632/33 F06

0 20 40 60 140 160 180 20080 100 120

INCREASING R8

DECREASING R8

Figure 6. Frequency Response

Documents

Dual rail to rail op-amp