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AN1730Using the MD1730 Ultra-Low Phase Noise CW Transmit
Beamformer for Medical Ultrasound Applications
INTRODUCTIONIn recent years, capabilities of medical ultrasound flowimaging systems have increased enormously. Colorflow imaging, Continuous Wave Doppler (CWD) andDoppler analysis that provide new flow image featuresare now commonly used. It is essential for theultrasound system to generate low-phase noise,high-quality CW transmission waveforms to get higher-quality Doppler echo signals.
This application note describes how Microchip’sMD1730 can help ultrasound systems achieve higher-quality, lower phase noise, focused CW arraytransmitters.
MD1730 is a very low-phase noise, 8-channel CWbeamforming waveform generation IC. It is designedfor CW Doppler mode in a medical ultrasound imagesystem.
CW BEAMFORMER TOPOLOGY
Normally, in CW mode, only ±2 to ±6V peak-to-peakvoltages are needed to drive the piezoelectric elementsin the ultrasound transducer probe. Therefore, theMD1730 circuit has been designed using thehigh-speed, low-voltage and low-time jitter CMOStechnology. The MD1730 provides an ultra-low phasenoise CW waveform, a high resolution CW frequencydivider and the per-channel delay timer for CWbeamforming function. These features help provideeight frequency-programmable CW sources withphase delay beamforming functions in a small 6 x6 mm QFN package. It helps save significant PCB realestate for portable medical ultrasound system. Figure 1shows a typical beamforming application for focusedCWD in a medical ultrasound system.
FIGURE 1: Forced CWD Beamforming in Medical Ultrasound System.
Author: Ching Chu Microchip Technology Inc.
B.F+Mixer
VCW-
-1 to - V
GND Ther.PAD
-10V
SUB
VGN CNF
EN
CW0
VNF
CLKP
CLKN
SDO
SDI
CSN
SPI
SCK
CW3
VPF
CWFre.Dvdr& PhaseDelay
CW2
CW1
TXRW
HIZ[7:0]
VLL
CLK
CLK
CBE1
CKB0
Ch0
SPIM
LVDS CLK
CBE0,1
VLL
CBE0
CKB1
U1 MD1730
VCW+
VCW-
+10V
VGP
+2.5V
VLL
+1 to + V
VCW+
+5V
VDD CPF
Ch7
CW4
CW7
CW6
CW5
VNF
VPF
VCW+
VCW-
Ch1~6
LNA
IN0
IN3
IN2
IN1
IN4
IN7
IN6
IN5
GND
U4 AFECW
Processor
+1.8V
VDD VCW
+3.3V
LNA
LNA
LNA
LNA
LNA
LNA
LNA
CW TxFocusBeamForming
CW RxEcho
U3 HV SW U3 HV SW
CW DopplerDetectingVolume
Where VS is he Sound Speed In Tissue.Where VB is the Velocity of the Flow.
MoreChannels
MoreChannels
MoreChannels
MoreChannels
with CW TxBeamformingDelay(PHDCh)
with CW RxBeamformingDelay(PHDCh)
B-ModeHV PulserOutput& T/R SWs
B-ModeHV PulserOutput& T/R SWs
UltrasoundTransducerProbe
2016 Microchip Technology Inc. DS00002307A-page 1
AN1730
MD1730 WORKING WITH HIGH VOLTAGE ANALOG SWITCHES
The ultra-low phase noise, high-speed and low-voltageoutputs of the MD1730 cannot withstand thehigh-voltage B-mode transmit pulse voltages.Therefore, HV analog switches must be used to blockthe Tx pulser outputs from the MD1730 during B-mode.Figure 2 shows an example implementation whereMicrochip's HV2201 8-channel analog MUX is usedwith the MD1730. HV2201 has eight high-voltageanalog switches that can withstand a ±100V peak
voltage of transmit pulses. When the HV switches areon, their low on-resistance has an extremely lowcontribution to the overall phase noise and phaseretardation of the CW waveforms. One MD1730, whencombined with one HV2201, can be used with four setsof MD1715s and TC8020s to form an 8-channel,5-level ±100V high-end Tx pulser with ultra-low phasenoise CW digital beamformer. During B-modeoperation, MD1730 is disabled using its EN pin, and theHV2201 switches are turned off using its CLR pin. InCW mode, the MD1730 is enabled and the HV2201switches are turned on.
FIGURE 2: MD1730 CW Working with HV2201 HV Switch and MD1715 + TC8020 ±100V ±3A 5-Level Tx Pulser.
+10V
VGP
+ to + VVCW+
CW0VPF
VNF
EN
+2.5V
VLL
TXRW
SPIB
SDICSNSCK
CLKN
CLKPLVDS / SSLTClock Input
SPI&
Registers
GND
CW1
MD1730ThermalPad
-10V
SUB
VLL
CLK CKB0
CW7VPF
VNF
- to - VVCW-
VCW+
VCW-
HIZ[7:0]
CPFVPF
VNF
CNF
SDO QMSB
D0
CKB1
CBE1
VLL
CBE0
+5V
VDD
VGN
CLK
PHD7~0[7:0] CWFD[7:0]
PHD1[7:0] CWFD[7:0]ENAENA Q
CLK CLKQ
PHD7[7:0] CWFD[7:0]ENAENA Q
CLK CLKQ
PHD0[7:0] CWFD[7:0]ENAENA Q
CLK CLKQ
864
CLK
SCK
VCW+
VCW-
XDCR
XDCR
DLECL
SW0
DLECL
SW1
DLECL
SW2
DLESW6
DLECL
SW7
CLK
8-BITSHIFT
REGISTER
DIN
DOUT
LEVELSHIFTERS
OUTPUTSWITCHES
VNN VPP CLR LE GND VDD
LATCHES
CL
TX7
EN
SELPOSNEG
B/CW
LVL[3:2]POS[3:2]NEG[3:2]
VDD2
High SpeedGate Buffers
VDD2
VDD1
VDD1
VSSVDD1
High SpeedGate Buffers
ControlLogic andLevelTransla-tion
GND
MD17151 of 2-ch
TC80206 of 12-FET
+10V
VDD2
+10V
VDD1
+10V
AVDD+90V
SP1
+50VSP2
-90V
SN1
-50V
DP1
DN1
DP2
DN2
SN2
SP3
SN3
DP3
DN3
GP1
GN1
GP2
GN2
GP3
GN3
OP1
ON1
OP2
ON2
OP3
ON3
-10V
VSS
-10V
AVSSPADGND PAD VSUB
TX0
VDD2
High SpeedGate Buffers
VDD2
VDD1
VDD1
VSSVDD1
High SpeedGate Buffers
ControlLogic andLevelTransla-tion
MD17151 of 2-ch
TC80206 of 12-FET
+10V
VDD2
+10V
VDD1
+10V
AVDD+90V
SP1
+50VSP2
-90V
SN1
-50V
DP1
DN1
DP2
DN2
SN2
SP3
SN3
DP3
DN3
GP1
GN1
GP2
GN2
GP3
GN3
OP1
ON1
OP2
ON2
OP3
ON3
-10V
VSS
-10V
AVSSPADGND PAD VSUB
HV22018-ch HVAnalog Switch
EN
SELPOSNEG
B/CW
LVL[1:0]POS[1:0]NEG[1:0]
GND
B/CW LE +3.3V-100V +100V
CW/ B
CW_START
FPGA
FPGA
DS00002307A-page 2 2016 Microchip Technology Inc.
AN1730
FIGURE 3: MD1730 with Two HV7321 as Low-Phase Noise CW Beamformer.
VCW-
- to - V
GND Ther.PAD
-10V
SUB
VGN CNF
EN
CW0
VNF
CLKPCLKN
SDO
SDI
CSN
SPI
SCK
CW3
VPF
CWFre.Dvdr& PhaseDelay
CW2
CW1
TXRW
HIZ[7:0]
VLL
CLK
CLK
CBE1CKB0
Ch0
SPIM
LVDS CLK
CBE0,1
VLLCBE0
CKB1
U1 MD1730
VCW+
VCW-
+10V
VGP
+2.5V
VLL
+ to + V
VCW+
+5V
VDD CPF
Ch7
CW4
CW7
CW6
CW5
VNF
VPF
VCW+
VCW-
Ch1~6
X0
0 to+80V
VPF1
VNN1
VPP1
RGND
TX0
-0 to-80V
VPP0
VNN0
0 to-80V
0 to+80V
1 of 4 Channels
+5V
VDD
Decode&
LevelShift
CWIN0
NEG0
SEL0
NEG3
SEL3
CWIN3 U2 HV7321
GND
OTPN
+2.5V
VLL
PWS
POS3
VSUB
SUB
MODE
REN
CLK
POS0
TX1-3
RX1-3
Rx0RX0
VPF0
VNF0
VNF1
RGND
RTZSW
CWSW
TRSW
RXDMP
TRSW
+10V
VGP
-10V
OEN
VGN
CWIN2
CWIN1
Tx FPGA I/Os
ToOtherICs
CTRN[3:0]
OTP
DT[63:0]
X4
0 to+80V
VPF1
VNN1
VPP1
RGND
TX0
-0 to-80V
VPP0
VNN0
0 to-80V
0 to+80V
1 of 4 Channels
+5V
VDD
Decode&
LevelShift
CWIN0
NEG0
SEL0
NEG3
SEL3
CWIN3 U3 HV7321
GND
OTPN
+2.5V
VLL
PWS
POS3
VSUB
SUB
MODE
REN
CLK
POS0
TX1-3
RX1-3
Rx4RX0
VPF0
VNF0
VNF1
RGND
RTZSW
CWSW
TRSW
RXDMP
TRSW
+10V
VGP
-10V
OEN
VGN
CWIN2
CWIN1
+2.5V
ToOtherICs
ToOtherICs
2016 Microchip Technology Inc. DS00002307A-page 3
AN1730
MD1730 WORKING WITH HV7321 TX PULSER
For the higher integration levels required in portablemedical ultrasound systems with tighter PCB spacing,Microchip’s HV7321 ultrasound transmit pulser, alongwith MD1730, offer a better and simpler solution. Referto Figure 3.
HV7321 is specifically designed to work withlow-voltage, ultra-low phase noise CW waveformgenerators such as the MD1730. HV7321 is afour-channel, 5-level ±80V, 2.6A ultrasoundtransmitter. HV7321 has integrated T/R switches(TRSW) and RTZ switches (RTZSW) along withhigh-voltage analog CW switches (CWSW).
When in B-mode, all CW switches are off and theyblock the high-voltage pulses. When the HV7321 is inCW Mode-1, these CW switches are turned on. Theinput terminals of the CW switches on the HV7321(CWIN0-3) connect to the MD1730’s CW outputs(CW0-7).
With the built-in CW switches, the HV7321 output pinscan be directly connected to the ultrasoundtransducers. The HV7321's built-in high-voltage analogswitches act like a high-voltage MUX, blocking the highvoltages in B-mode and passing through thelow-voltage CW signals to the MD1730.
CONTROLLING THE MD1730 AND THE HV7321
During B-mode, the MD1730 does not need to beenabled. Setting EN = 0 will reduce power consump-tion. The user can turn off the MD1730’s clock on CLKPand/or CLKN for power saving.
If MD1730’s EN = 1, the user must set TXRW = 0, tomake sure the CW0-7 output are all in high Z state. Atthe same time, HV7321’s CWSW0-3 must be turnedoff, by setting the pin to MODE = 0. When theMD1730's CW signals are expected, the HV7321 is setto CW Mode-1.
The following steps should be taken to ensure properoperation:
1. Apply all power supply rails to both chips and setHV7321’s to OEN = REN = PWS = 1 along withMD1730’s to EN = 1 to enable both chips. Set allother logic input pins to zero.
2. Adjust the VCW+ and VCW- power supplies to therequired peak-to-peak voltage levels for CWoutput transmission. Please note that a higherpeak-to-peak transmission voltage will result inthe MD1730 dissipating more power. The powerdissipation of the MD1730 is proportional to thesquare of the peak-to-peak voltage (about 2 to12VP-P).
3. Set HV7321’s MODE = 1.
4. Program the MD1730 with the desired CWfrequency divider and delay settings for CWtransmission.
For more details, please see the MD1730 datasheet "8-Ch Ultra Low Phase Noise CW Trans-mitter with Beamformer" (DS20005586).
5. To place a channel in receive mode, set thechannel's SEL, NEG and POS pins to 0, 1 and1 respectively on the HV7321. To place achannel in CW transmit mode, set the channel’sSEL, NEG and POS to any other combinationother than 0,1 and 1 respectively on HV7321.This will put that channel of the HV7321 high-voltage Tx output in high Z mode, but it will turnon the channel’s CW switch (CWSW).
To set the MD1730's CW pin in high Z mode, setthe corresponding bit in the high Z register to 1.
6. Once the system is ready to perform CWDoppler measurement, assert TXRW high tostart the CW transmission on the selectedchannels.
LOW PHASE NOISE CLOCK INPUTS AND OUTPUT BUFFERS
MD1730’s built-in eight independent channels shareone pair of synchronization clock input pins:CLKP/CLKN. The IC can accept a clock frequency upto 250 MHz. These clock inputs can be connected asdifferential LVDS input, or as single-ended LVCMOS2.5V input.
If a higher CW frequency step resolution is needed,then the differential LVDS or SSTL2.5V type clock inputmethod can be used, as shown Figure 4; a 100differential termination resistor must be connected asclosely as possible to the CLKP and CLKN pins.
LVDS clock line pair traces on the PCB should bedesigned as two 50 transmission lines with respect toGND plane, and the differential traces should be run asclosely as possible after they leave the multi-LVDSbuffer IC.
However, for the best phase noise performance, use anLVCMOS-2.5V single-ended type clock input, asshown in Figure 4. The clock frequency should be inthe range of 80 to 120 MHz. Select a very low phasenoise LVCMOS 2.5V clock buffer, like Microchip’sPL133-47. The input clock of the buffer IC should befrom an ultra-low phase crystal oscillator source.
If the CLKP input pin is connected to a single-endedLVCMOS-2.5V buffer output, then the CLKN input pinmust be connected to 1.25V with a 0.1 µF bypasscapacitor to GND.
DS00002307A-page 4 2016 Microchip Technology Inc.
AN1730
To use as an inverting phase of clock input, the CLKPand CLKN input pins can be swapped. CLKN should beconnected to the buffer output, and CLKP should beconnected to 1.25V and bypassed with a capacitor toGND.
In the single-ended clock input case, a 33 reversetermination resistor must be placed in-series with eachbuffer output. These resistors should be placed close tothe buffer output pins. The clock trace on the PCBshould be designed as a 50 transmission line withrespect to the GND plane. Figure 4 shows this reversetermination method. The clock trace reaches to theMD1730 clock input pin, so a 50 resistor will no longerbe needed to terminate to GND.
Following this method, the user can save powerconsumption for the clock distribution circuit. For thebest phase noise performance, the value of the reversetermination resistor should be optimized based on theCWD mode phase noise results.
FIGURE 4: Configuration as LVDS or LVCMOS - 2.5V Single-Ended Clock Inputs.
INTERFACE AND REGISTERS CONFIGURATION
MD1730 has two registers that can be configured viaSPI interfaces. The first register is the per-channelbeamforming delay register PHDch<7:0>. The secondregister is the CW frequency divider number registerCWFD<7:0>. Normally, it only needs to be configuredonce, and all the MD1730 chip’s CWFD registersshould have the same number.
Multiple MD1730s can be daisy-chained and pro-grammed as shown in Figure 5. Use the normal SPIoperation mode to write the first type (PHDch<7:0>) ofregister and use the Broadcasting mode to set theCWFD<7:0> quickly on each chip.
2.5V
CLK0
MD1730U2 U4U1MD1730 MD1730
PL133-47CLK Buffer
EN
TXRW TXRW
TXRW
TXRWEN ENEN
EN
CLKP CLKN CLKP CLKN CLKP CLKN
1.25V DC
0.1uF 0.1uF 0.1uF
Single-EndedLVCMOS Clock Line
VLL
2.5V
VLL VLL
2.5V 2.5V
80-150MHzClock OSC.
(from FPGA)
REF CLK1
CLK3GND 33ohm
GND GND GND
100VCC
MD1730U2 U4U1MD1730 MD1730
EN
TXRW TXRW
TXRW
TXRWEN ENEN
EN
CLKP CLKN CLKP CLKN CLKP CLKNDiffertial LVDSClock Line-Pair
CLK Buffer
2.5V
VLL
2.5V
VLL
2.5V
VLL
2.5V
ClockSource
(from FPGA)
Q0
Q1... ...Q3
IN
100 100
SY89832U
GNDGND GND
GND
2016 Microchip Technology Inc. DS00002307A-page 5
AN1730
NORMAL SPI MODE VS. SPI BROADCASTING MODE
The MD1730 SPI interface circuitry is designed todirectly connect to a normal SPI on a FPGA I/O pins. Towrite into the MD1730 SPI registers, the user mustalways send the MSB data bit first.
FIGURE 5: Multiple MD1720 Devices SPI Daisy Chain.
When SPIB = 0, the chip is configured in normal SPIread/write mode. In this mode, multiple MD1730s canbe configured using the daisy chain.
When SPIB = 1, the chip will support the Broadcastingmode, in which multiple MD1730s can be programmedwith the same value simultaneously. This high-speedBroadcasting mode reduces the programming timesignificantly and can be used to program thebeamforming CW frequency registers.
In addition, all the data being written into the registersin each chip during the broadcasting mode can be readout by the normal SPI read operations to be verified.This read-back feature helps with software debuggingand testing.
EXAMPLE OF SPI WRITE OPERATION
The following is a 1-byte writing example for theregister at ADD = 0011b with the dataD<7:0> = 01010101 when SPIB = TXRW = 0:
1. The write operation starts with setting CSN tolow.
2. SDI data is shifted into the shift register:
D<12> = 1 (W/R bit is set high); writing isenabled.
ADD<11:8> = 0011b, address for channel 3’sphase delay register.
D<7:0> = 01010101b, data to be written intochannel 3’s phase delay register.
The SDI data is shifted in at the rising edge ofSCK.
3. Once the complete data has been shifted in, theCSN should be set high to finish the writingoperation. The SDI data is latched intochannel 3’s phase delay register on the risingedge of CSN. CSN has to be kept high for aminimum of two SCK cycles for the data to bewritten into the appropriate register.
In the case of eight chips daisy-chained together, thereshould be 13 x 8 = 104 cycles of SCK before the CSNis set high.
MD1730 can also be used in Broadcasting mode towrite several daisy-chained chips with the same data.The Broadcasting mode can be used to reduce the timerequired to write using SPI if several MD1730 chipshave to be programed with the same data. An exampleof writing to MD1730 in broadcasting mode is givenbelow:
1. Set TXRW = 0 and SPIB = 1. Set CSN = 0(broadcasting operation starts).
2. Shift in the following SDI data to the firstMD1730 chip with SCK clock:
D<12> = 1 (W/R bit is set high), writing isenabled.
ADD<11:8> = 0011b, address for thechannel 3’s phase delay register.
D<7:0> = 01010101, data to be written into thechannel 3’s phase delay register.
SDI SDO
SCK CS
TXRW
13bit Shift Reg.
SPIB
D0
Q12
SDISDO
SCK CSN
TXRW
13bit Shift Reg.
SPIB
D0
Q12
MD1730U2 U8
TXRW
SCK
CSN
SDI
FPGA
SDO
U1MD1730 MD1730
SPIB
SDI SDO
SCK CS
TXRW
13bit Shift Reg.
SPIB
D0
Q12
SDISDO
SCK CSN
TXRW
13bit Shift Reg.
SPIB
D0
Q12
SDI SDO
SCK CS
TXRW
13bit Shift Reg.
SPIB
D0
Q12
SDISDO
SCK CSN
TXRW
13bit Shift Reg.
SPIB
D0
Q12
DS00002307A-page 6 2016 Microchip Technology Inc.
AN1730
The SDI data is shifted in at the rising edge ofSCK.
In broadcasting mode, the same set of datashifted into the first chip is sent to all theMD1730 chips along the daisy chain. WhenSPIB = 1, an internal switch connects the SDIand SDO directly, bypassing the shift register.
3. Once the complete data has been shifted in, theCSN should be set high to finish the writingoperation. The SDI data is latched into eachchip’s channel 3 phase delay register on therising edge of the CSN signal. CSN has to bekept high for a minimum of two SCK cycles forthe data to be written into the appropriateregister.
SPI READ OPERATION EXAMPLES
The following is an example to read 2-byte data fromthe MD1730 register at ADD = 0011b (channel 3’sphase delay register) when SPIB = TXRW = 0:
1. Set CSN = 0. Read-write operation starts.
2. SDI shifts in the following data:
D<12> = 0 (W/R bit is set low). Reading isenabled.
ADD<11:8> = 0011b, address for channel 3’sphase delay register.
D<7:0> = X, for a read operation, the data fieldis ‘don’t care’.
The SDI data is shifted in at the rising edge ofSCK.
3. Once the complete data has been shifted intothe SPI, the CSN is set high. While CSN is high,the MD1730 fetches the data located atADD<11:9> = 0011b and places it in its internalshift register.
CSN has to be kept high for a minimum of twoSCK cycles for the data to be fetched andplaced into the internal shift register.
4. CSN is set low and during the next 13 SCK clockcycles, the fetched data in the internal shiftregister is clocked out on the rising edge of SCKfrom the SDO of the MD1730.
POWER SUPPLY DECOUPLING
MD1730 is designed for ultra-low phase noiseoperation. However, the overall phase noise will not beonly be dependent on the MD1730 internal circuitdesign and manufacture, but also dependent on thefollowing application conditions:
• power supply ripple noise
• power supply switching spike noise
• power supply topology
• power supply circuit layout
• selection and layout of the decoupling capacitors for the MD1730's power pins
• PCB stack-up and ground planes
It is highly recommended that the user selects anultra-low ripple noise and well-filtered DC power sourcefor each one of the six power supplies required by theMD1730.
It is also recommended to use a low-noise, isolated,DC/DC power supply followed by a linear, low-dropout,post regulator.
A suitable power supply topology for this application isa push-pull converter. This converter has goodefficiency, low output noise and high common modenoise isolation.
Every design must pass EMI/RFI regulationcompliance for medical equipment. Typical methods tomeet these requirements include using low-inductancePCB layout techniques and adding R-C snubbers atswitching nodes.
The DC-to-DC converter circuit’s DC input and outputvoltage node to the ground must have considerablebypassing capacitors to achieve lower switching rippleand spike noise filtering. It is very important to selectlow ESR/ESL ceramic surface mount capacitors.
The switching power supply isolation transformerdesign must have good electrical and magnetic shield-ing, ground and flex bindings.
Ensure that the switching noise from the DC/DCconverter does not contaminate the MD1730's groundplane.
An example of a power supply ground connections toensure a low-noise power supply is shown in Figure 6.
It is recommended to define a localized copper area foreach circuitry block of the DC-to-DC converters aseach block circuitry common ground. All thecomponents within the circuitry block have to be placedon a localized common ground area. Then all localground traces, as short as possible, must connect toeach other first. Then, the local ground summing nodegoes through via(s) connecting to the second-layerground copper plane. After that, use only one point,such as one big via to connect this localized commonground to the GND plane of the PCB. This methodshould also be used for the post LDO linear voltageregulators.
Using an LDO at the output of DC-to-DC converterhelps improve voltage regulation, as well as reducenoise from the DC-to-DC converter in the100 Hz to 100 kHz range.
Selecting correct decoupling capacitors (value andtype) is important. It is recommended that the decou-pling capacitors used are low ESR/ESL, multi-layerceramic chip capacitors. Table 1 lists the recom-mended capacitors at each of the power supply pins ofthe MD1730.
2016 Microchip Technology Inc. DS00002307A-page 7
AN1730
The LDOs should be placed as close to the MD1730 asfeasible. It is recommended that the maximum tracelength used to connect the MD1730's power pins to thedecoupling capacitors does not exceed 5 mm. Therecommended width of the traces should be between0.3 mm and 0.5 mm.
The switching frequencies of the DC/DC convertersshould be synchronized to the CW frequency or theinput clock frequency.
FIGURE 6: Ultra-low Noise Multi Rail Power Supply Example.
MD1730 CW OUTPUT PHASE NOISEMEASUREMENT
Since the MD1730's phase noise is extremely low, themeasured phase noise can be very easily affected byexternal noise sources.
The equipment chosen to do the phase noise measure-ment should be able to measure a large amplitudesquare wave at 5 MHz.
The measurement setup has to be shielded so thatthere is no external background EMI/RFI noise thatcould affect the measurement.
Figure 7 shows the principle of the MD1730 CW outputwaveform phase noise measurement.
In this setup, an RF mixer is used as phase detector.The mixer must be a wide-bandwidth symmetric-diodering type. The two CW waveforms are at 90 degreesphase-shifted with respect to each other. The twochannels under evaluation can belong to one or twoDUT chips of MD1730. Both CW channels can bedriven by a single clock source CLK. The clock sourceand the buffers phase noise will be rejected by thesymmetric mixer. But the CW channel frequencydivider and channel phase delay counter circuits areindependent. The phase noise generated by the twochannels cannot be considered to be correlated toeach other. Therefore, the final phase noisemeasurement should be considered as the sum of thetwo independent MD1730 channels noises.
Phase noise measurements on the MD1730 are shownin Figure 8.
TABLE 1: POWER SUPPLY PIN DECOUPLING CAPACITORS
Supply Rail De. Cap. Value/Voltage Rating Capacitor Type
VLL to GND 1.0 µF/10VDC Low ESR/ESL CeramicX5R or X7R0603/0402
VDD to GND 1.0 µF/10Vdc
VGP to GND 2.2 µF/16VDC
VGN to GND 2.2 µF/16VDC
VCW+ to GND 1.0 µF/16VDC
VCW- to GND 1.0 µF/16VDC
CPF to VCW+ 1.0 µF/16VDC
CNF to VCW- 1.0 µF/16VDC
Note: One per each power supply pin.
+10V
D12
FB6
FB7 MIC5270-10V
D15
FB4
FB5
L5
D9
COM2
L6 D10
D4
D6
VREF VDD
SH
ISO
L1
D1
D5
D7
+10.8 to 12.6V
RTN1GND
RC
OUTA
OUTB
RAMPILIM
COMP
FB
Fd.FwrdRampCurrentLimit
FB1 +5.0VL2 L3D2
D3
D8
D11
FB2
FB3
COM1
+2.5V
D13
VDD VLL
MIC5209+1 to +8V
D14
FB10
-1 to -8V
D16
FB8
FB9
VGPVCW+
VCW-VGN
DAC
MIC5209
MIC5209MIC5209
VCW_ADJ
R1
R2
R3
R4
R5
R6
R7
R8
R9
R10
R11
R12
R13
FB
FB
FB
FB
+11V
-11V
MIC3809
M1
M2
C1
C2
C3
C4
C5
C6
C7
C8
C9
C10
C11
C12
C13
C14
C15
C16
C17
C18
C19
C20
C21
C22
C23
C24
C25
C26
C27
R14
R15
R16
R17
R18
R19
R20
L4
L7
GND GND
GND
GND
GND
GND
T1
1
2
3
4
5
6
7
8
910
+VDC
R22
R21
LM337
C8'
DS00002307A-page 8 2016 Microchip Technology Inc.
AN1730
FIGURE 7: MD1730 CW Output Phase Noise Measurement Setup.
FIGURE 8: MD1730 CW Output Typical Phase Noise.
Very LowPhase NoiseClock Source
Mixer
CW0
CW1
DUT
90o
0o
Low-PassFiler
SpectrumAnalyzer
CLK
0 1kHz
-180
-170
-160
-150
-140
-130
-120
-110
-100
0.01 0.1 1 10 100
Phas
e N
oise
(dB
c/H
z)
Offset Frequency (kHz)
MD1730 CW Output Phase Noise at 5 MHz, Offset 10 Hz to 100 kHzMixer + Lowpass + HP4195A with ATR -20 dB, RBW 10 Hz
2016 Microchip Technology Inc. DS00002307A-page 9
AN1730
NOTES:
DS00002307A-page 10 2016 Microchip Technology Inc.
Note the following details of the code protection feature on Microchip devices:
• Microchip products meet the specification contained in their particular Microchip Data Sheet.
• Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the intended manner and under normal conditions.
• There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data Sheets. Most likely, the person doing so is engaged in theft of intellectual property.
• Microchip is willing to work with the customer who is concerned about the integrity of their code.
• Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not mean that we are guaranteeing the product as “unbreakable.”
Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of ourproducts. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such actsallow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.
Information contained in this publication regarding deviceapplications and the like is provided only for your convenienceand may be superseded by updates. It is your responsibility toensure that your application meets with your specifications.MICROCHIP MAKES NO REPRESENTATIONS ORWARRANTIES OF ANY KIND WHETHER EXPRESS ORIMPLIED, WRITTEN OR ORAL, STATUTORY OROTHERWISE, RELATED TO THE INFORMATION,INCLUDING BUT NOT LIMITED TO ITS CONDITION,QUALITY, PERFORMANCE, MERCHANTABILITY ORFITNESS FOR PURPOSE. Microchip disclaims all liabilityarising from this information and its use. Use of Microchipdevices in life support and/or safety applications is entirely atthe buyer’s risk, and the buyer agrees to defend, indemnify andhold harmless Microchip from any and all damages, claims,suits, or expenses resulting from such use. No licenses areconveyed, implicitly or otherwise, under any Microchipintellectual property rights unless otherwise stated.
2016 Microchip Technology Inc.
Microchip received ISO/TS-16949:2009 certification for its worldwide headquarters, design and wafer fabrication facilities in Chandler and Tempe, Arizona; Gresham, Oregon and design centers in California and India. The Company’s quality system processes and procedures are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping devices, Serial EEPROMs, microperipherals, nonvolatile memory and analog products. In addition, Microchip’s quality system for the design and manufacture of development systems is ISO 9001:2000 certified.
QUALITYMANAGEMENTSYSTEMCERTIFIEDBYDNV
== ISO/TS16949==
Trademarks
The Microchip name and logo, the Microchip logo, AnyRate, dsPIC, FlashFlex, flexPWR, Heldo, JukeBlox, KeeLoq, KeeLoq logo, Kleer, LANCheck, LINK MD, MediaLB, MOST, MOST logo, MPLAB, OptoLyzer, PIC, PICSTART, PIC32 logo, RightTouch, SpyNIC, SST, SST Logo, SuperFlash and UNI/O are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries.
ClockWorks, The Embedded Control Solutions Company, ETHERSYNCH, Hyper Speed Control, HyperLight Load, IntelliMOS, mTouch, Precision Edge, and QUIET-WIRE are registered trademarks of Microchip Technology Incorporated in the U.S.A.
Analog-for-the-Digital Age, Any Capacitor, AnyIn, AnyOut, BodyCom, chipKIT, chipKIT logo, CodeGuard, dsPICDEM, dsPICDEM.net, Dynamic Average Matching, DAM, ECAN, EtherGREEN, In-Circuit Serial Programming, ICSP, Inter-Chip Connectivity, JitterBlocker, KleerNet, KleerNet logo, MiWi, motorBench, MPASM, MPF, MPLAB Certified logo, MPLIB, MPLINK, MultiTRAK, NetDetach, Omniscient Code Generation, PICDEM, PICDEM.net, PICkit, PICtail, PureSilicon, RightTouch logo, REAL ICE, Ripple Blocker, Serial Quad I/O, SQI, SuperSwitcher, SuperSwitcher II, Total Endurance, TSHARC, USBCheck, VariSense, ViewSpan, WiperLock, Wireless DNA, and ZENA are trademarks of Microchip Technology Incorporated in the U.S.A. and other countries.
SQTP is a service mark of Microchip Technology Incorporated in the U.S.A.
Silicon Storage Technology is a registered trademark of Microchip Technology Inc. in other countries.
GestIC is a registered trademarks of Microchip Technology Germany II GmbH & Co. KG, a subsidiary of Microchip Technology Inc., in other countries.
All other trademarks mentioned herein are property of their respective companies.
© 2016, Microchip Technology Incorporated, Printed in the U.S.A., All Rights Reserved.
ISBN: 978-1-5224-1032-4
DS00002307A-page 11
DS00002307A-page 12 2016 Microchip Technology Inc.
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