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Communication Systems Laboratory
New Results in Coding and Communication Theory
Communication Systems Laboratoryhttp://www.ee.ucla.edu/~csl/
Rick Wesel
At the Aerospace CorporationAugust 11, 2008
BikeXie
Yuan-Mao Chang
Tom Courtade
Jiadong Wang
MiguelGriot
Communication Systems Laboratory
Recent Results
• A more efficient LDPC decoding algorithm
• Dynamically scheduled LDPC decoder that converge to a better frame error rate than previous state-of-the-art.
• A powerful family of low-rate turbo codes for “rate-less”applications at the physical layer.
• Turbo Code with closest-to-Shannon performance through novel nonlinear labeling.
• New information theoretic results and nonlinear turbo codes for multi-rate broadcast.
2
Communication Systems Laboratory
Recent Results
• A more efficient LDPC decoding algorithm
• Dynamically scheduled LDPC decoder that converge to a better frame error rate than previous state-of-the-art.
• A powerful family of low-rate turbo codes for “rate-less”applications at the physical layer.
• Turbo Code with closest-to-Shannon performance through novel nonlinear labeling.
• New information theoretic results and nonlinear turbo codes for multi-rate broadcast.
Communication Systems Laboratory
Simultaneous (Flooding) Schedule
• On every iteration– All variable nodes are
simultaneously updated– All check nodes are
simultaneously updated
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Communication Systems Laboratory
Standard Sequential Schedule (SSS)a.k.a Layered Belief Propagation (LBP)
• Update messages sequentially:– [Mansour 03] (CN sequence)– [Kfir 03] (VN sequence)– [Hocevar 04] (LBP)– [Sharon 04] (Serial Schedule)– [Zhang 05] (Shuffled BP)– [Radosavljevic 05]
Communication Systems Laboratory
Results N=1944 Rate=1/2
0 5 10 15 20 25 30 35 40 45 5010
-4
10-3
10-2
10-1
100
Iterations
FE
R
Eb/No = 1.75 dB
Simultaneous (Flooding)LBP
Layered belief propagation isabout twice as fast a flooding.
4
Communication Systems Laboratory
Informed Dynamic Scheduling• Sequential scheduling is a good idea• What is the best sequence of updates?• Use the current information in the graph to
choose the next message to be sent• This is called Informed Dynamic Scheduling
(IDS)
Communication Systems Laboratory
Residual Belief Propagation (RBP) [Elidan 06]
• Define residual as:
• As BP converges, the residuals go to 0• RBP is a greedy algorithm that propagates
the message with the largest residual
new oldr m m= −
5
Communication Systems Laboratory
• Messages are Log-Likelihood Ratios (LLRs)
• Message-generation equations:
RBP for LDPC decoding
( )\j i a j j
j i
v c c v va N v c
m m C→ →∈
= +∑
( )\2 atanh tanh
2b i
i j
b i j
v cc v
v N c v
mm →
→∈
⎛ ⎞⎛ ⎞= × ⎜ ⎟⎜ ⎟⎜ ⎟⎝ ⎠⎝ ⎠
∏
( )( )
0log
1j
j
p v
p v
⎛ ⎞=⎜ ⎟⎜ ⎟=⎝ ⎠
Communication Systems Laboratory
• Initially propagate the channel information
• Propagate message with biggest residual
• The variable-to-check messages that change will have the same residual so they are the biggest
• Therefore, RBP can be simplified– Propagate check-to-variable
message with biggest residual– Propagate variable-to-check
messages that change
RBP for LDPC decoding
6
Communication Systems Laboratory
Results N=1944 Rate=1/2
0 5 10 15 20 25 30 35 40 45 5010
-4
10-3
10-2
10-1
100
Iterations
FE
R
Eb/No = 1.75 dB
Simultaneous (Flooding)LBPRBP
Residual Belief Propagationstarts out fast but hits a nastyerror floor.
Communication Systems Laboratory
Dynamic Node-wise Scheduling (NS)
• Find the check-to-variable message with the biggest residual.
• Update the check-node.• Update the variable-to-
check messages that change.
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Communication Systems Laboratory
A better answer in fewer iterations:Results N=1944 Rate=1/2
0 5 10 15 20 25 30 35 40 45 5010
-5
10-4
10-3
10-2
10-1
100
Iterations
FE
R
Eb/No = 1.75 dB
Simultaneous (Flooding)
LBPRBP
NS
Communication Systems Laboratory
We understand faster, but why better?
• Performance plots show that informed dynamic scheduling strategies perform not only faster but better than LBP.
• There are several noise realizations that aren’t corrected after 200 LBP iterations but are corrected after few ANS iterations.
• This difference can’t be explained with the argument of the “wasted” updates.
• Informed Dynamic Scheduling solves “trapping-set” errors that neither LBP nor flooding scheduling can solve.
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Communication Systems Laboratory
• RBP greediness makes it converge faster but less often
• Node-wise Scheduling (NS) simultaneously propagates all the outgoing messages from a check node
• The check-node updated is the one that has the message with the biggest residual
• This means that correcting messages are simultaneously sent to all variable nodes that could be in error
• NS converges slower than RBP but more often
Node-wise Scheduling (NS)
Communication Systems Laboratory
IDS “Iterations”• There aren’t iterations in IDS strategies
• In order to compare the scheduling strategies we count an iteration after the number of check-to-variable messages propagated is the same as in a flooding or LBP iteration
• The message generation complexity of all the strategies is the same
• Residual computation makes the IDS strategies more complex than flooding and LBP
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Communication Systems Laboratory
• Residual computation requires the values of the messages to be propagated.
• Many of those computations are then “wasted” since many of those messages aren’t propagated.
• Using the min-sum check-node update to compute residuals significantly reduces the complexity.
• Approximate RBP (ARBP) and Approximate NS (ANS) are the min-sum versions of RBP and NS respectively.
Complexity
Communication Systems Laboratory
– Check-to-variable message equation:
–
– Thus a check-node update involves:• Find the two variable-to-check messages with
the smallest reliabilities• Compute the signs of the check-to-variable
messages• Assign the correct reliability
Min-sum
( )( ) ( ) ( )
\\
sgn mini j b i b i
b i jb i j
c v v c v cv N c vv N c v
m m m→ → →∈∈
= ⋅∏
10
Communication Systems Laboratory
Results N=1944 Rate=1/2
0 5 10 15 20 25 30 35 40 45 5010
-5
10-4
10-3
10-2
10-1
100
Iterations
FE
R
Eb/No = 1.75 dB
RBPARBPNSANS
Communication Systems Laboratory
Results N=1944 Rate=1/2
1 1.5 2 2.510
-5
10-4
10-3
10-2
10-1
100
Eb/No
FE
R
FloodingLBPANS
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Communication Systems Laboratory
Results 802.11n code rate 1/2
0 20 40 60 80 100 120 140 160 180 20010
-5
10-4
10-3
10-2
10-1
100
Iterations
FE
R
Eb/No = 1.75 dB
Simultaneous (Flooding)LBPARBPANS
Communication Systems Laboratory
Results 802.11n code rate 5/6
0 20 40 60 80 100 120 140 160 180 20010
-5
10-4
10-3
10-2
10-1
100
Iterations
FE
R
SNR = 6 dB
Simultaneous (Flooding)LBPARBPANS
12
Communication Systems Laboratory
Recent Results
• A more efficient LDPC decoding algorithm
• Dynamically scheduled LDPC decoder that converge to a better frame error rate than previous state-of-the-art.
• A powerful family of low-rate turbo codes for “rate-less”applications at the physical layer.
• Turbo Code with closest-to-Shannon performance through novel nonlinear labeling.
• New information theoretic results and nonlinear turbo codes for multi-rate broadcast.
Communication Systems Laboratory
Recent Results
• A more efficient LDPC decoding algorithm
• Dynamically scheduled LDPC decoder that converge to a better frame error rate than previous state-of-the-art.
• A powerful family of low-rate turbo codes for “rate-less”applications at the physical layer.
• Turbo Code with closest-to-Shannon performance through novel nonlinear labeling.
• New information theoretic results and nonlinear turbo codes for multi-rate broadcast.
13
Communication Systems Laboratory
Nonlinear Turbo Codes
TCM
Interleaver
TCM
0k
0k
k
• All existing turbo codes use linear convolutional component codes.
• Miguel Griot developed new tools that allow us to design and analyze nonlinear component trellis codes.
Communication Systems Laboratory
Traditional Linear Turbo Codes
NLTC
S
LUTbk
cnνΠ
1
2
State Machine
Linear Function
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Communication Systems Laboratory
Nonlinear Turbo Codes
NLTC
S
LUTbk
cnνΠ
1
2
State Machine
ANY Function
Communication Systems Laboratory
Motivations• Applications where a non-uniform distribution
of ones and zeros are required for maximum transmission rate. (Linear codes provide equally likely ones and zeros).
• Higher-order modulations:
CC
Interleaver
CC
0k
0k
kMapper
Mapper
Trellis codedmodulation
15
Communication Systems Laboratory
Higher-order modulations• The serial concatenation of a convolutional
code with a mapping could be too restrictive.• We can use any function that assigns
constellation points to each of the branches of the trellis.
NLTC
S
LUTbk
cnνΠ
1
2
State Machine
f(u,v)u
A constellation
point.
Communication Systems Laboratory
Analytical Bit Error Rate bound• We provide a method to predict the BER of parallel
concatenated non-linear codes over asymmetric channels, in particular the Z-Channel, under Maximum Likelihood decoding.
• We extend the uniform interleaver analysis proposed in [Benedetto ‘96].
• Uniform interleaver: given the two constituent codes, average over all possible interleavers of a certain length K.
• Key difference: nonlinearity of the constituent codes. We cannot assume that the all-zero codeword is transmitted. We need to average over all possible codewords.
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Communication Systems Laboratory
A new uniform interleaver• A new probabilistic device:
• Uniform interleaver for linear codes (Benedetto): “A uniform interleaver of length k is a probabilistic device that maps a given input word of Hamming weight w into all distinct permutations of it with equal probability”.
– This definition is useful only when assuming the all-zero codeword is transmitted.
• New definition for ANY code: “A uniform interleaver of length k is a probabilistic device the chooses between all possible positionpermutations with equal probability. Then, for each position, the value of the symbol can be changed to any other value with equal probability”.
– This new definition includes the linear case and leads to similar conclusions for both linear and nonlinear constituent codes.
Communication Systems Laboratory
Trellis structure and effective free distance
• The new uniform interleaver analysis allows to show that a recursive encoder is required for nonlinear codes as well.
• Benedetto showed that an important metric to maximize in the constituent linear codes is the effective free distance. We extend this notion for nonlinear codes:
• Effective free distance: minimum distance in the output produced by any two possible input words with Hamming distance 2.
• This definition includes the linear case.
17
Communication Systems Laboratory
Example: 2 bits/s/Hz 8PSK
• Constrained capacity: 2.8 dB.• We compare against the best previously published
16-state turbo code [Fragouli’01].
• Goal: maximize the effective free distance, where the distance in this case is the squared Euclidean distance.
416-St CC Mapper
3
416-St CC Mapper
3
Interleaver Nonlinear trellis code
Communication Systems Laboratory
Example: 2 bits/s/Hz 8PSK
• Achieving greater effective free distance than linear codes:– This is a fully connected trellis: given any two states S1 and
S2, there are 16 trellis paths from S1 to S2 after two trellis sections.
– Using a linear convolutional code and a mapper, all the searches we and previous works have done, have at least on pair of those paths that have a distance of
0
1
15
S1
S2
21 0.5858d =
22 2d =
212 1.171573d =
18
Communication Systems Laboratory
Example: 2 bits/s/Hz 8PSK
• Achieving greater effective free distance than linear codes:
– We found a nonlinear labeling that guarantees that for each pair of those paths, there is at least one trellis sections where the constellation points have squared Euclidean distance 2.
– There could still be a path in more than 2 trellis sections withdistance less than 2. By a search in the trellis structure we avoid that.
– The resulting nonlinear constituent code has an effective free distance equal to 2.
0
1
15
S1
S2
21 0.5858d =
22 2d =
Communication Systems Laboratory
0.2 dB gain for rate-2/3, 16-statesover the best published 10,000 bit code.
2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.810
-7
10-6
10-5
10-4
10-3
10-2
10-1
100
BE
R
Eb/N0 [dB]
[Fragoul'01]
Bound [Fragouli'01]
PC-NLTCM
Bound PC-NLTCM
19
Communication Systems Laboratory
Observations• Interleaver design plays an important role in
the code’s performance as shown in [Fragouli’01]. The uniform interleaver analysis averages over all possible interleaver, which explains the difference in the error flour between simulations and the bound.
• However, the BER bounding analysis helps in the design process.
Communication Systems Laboratory
Recent Results
• A more efficient LDPC decoding algorithm
• Dynamically scheduled LDPC decoder that converge to a better frame error rate than previous state-of-the-art.
• A powerful family of low-rate turbo codes for “rate-less”applications at the physical layer.
• Turbo Code with closest-to-Shannon performance through novel nonlinear labeling.
• New information theoretic results and nonlinear turbo codes for multi-rate broadcast.
20
Communication Systems Laboratory
Broadcast Channels• One transmitter broadcasts information
messages to several receivers.
• Receivers decode messages without collaboration.
• Still an open problem. (outer bounds [Sato78], [Marton79], inner bounds [Van75], [Cover75], [Hajek79], [Marton79])
39
XY1
Y2
( )1 |p y x
( )2 |p y x
Communication Systems Laboratory
Degraded Broadcast Channel• Physically Degraded Broadcast Channels
– The worse channel is a further distortion of the better channel.
• Stochastically Degraded Broadcast Channels– The marginal distribution of the worse
channel could have been produced by a further distortion of the better channel.
40
( )1 1
2 1 2 1| ( | ) ( | )y
p y x p y x q y yy∈
= ∑
( )1 |p y x ( )2 1|q y yX Y1 Y2
21
Communication Systems Laboratory
• The capacity region is the convex hull of the closure of all rate pairs (R1, R2) satisfying
• for some joint distribution
41
1 1 2( ; | ),R I X Y X≤
2 2 2( ; ),R I X Y≤
2 1 2 2 2 1 2( , , , ) ( ) ( | ) ( , | ).p x x y y p x p x x p y y x=
( )1 |p y x ( )2 1|q y yX Y1 Y2( )2|p x xX2
Degraded Broadcast Capacity Region[Cover72][Bergmans73][Gallager74]
Communication Systems Laboratory
Successive Encoding and Decoding
• Successive, but joint, encoding
• User 2 is decoded treating user 1 as noise.• Successive decoding for user 1
42
1W
2W Joint Encoder
Encoder 2nX2
nX
1nY
Decoder 2
Decoder 1“Subtract”
2ˆ nX
1nY
2( )p x 2( | )p x x
( )1 |p y x ( )2 1|q y yX Y1 Y2( )2|p x xX2
22
Communication Systems Laboratory
Degraded Gaussian Broadcast Channel– Channel Model
– General Transmission Strategy
43
+
+ +
Successive Decoder
Decoder 2
1W
2W
nX
2nY
1nY
nNΔ1nN
1nN
1W
2W
Joint Encoder
X2Y
1Y
NΔ1N
1N
+
+ +
( )210,σ∼ N
( )20,σΔ∼ N( )210,σ∼ N
Communication Systems Laboratory
Degraded Gaussian Broadcast Channel– Channel Model
– Optimal Transmission Strategy [Bergmans74]
44
+
+ +
Successive Decoder
Decoder 2
1W
2W
nX
2nY
1nY
nNΔ1nN
1nN
X2Y
1Y
NΔ1N
1N
+
+ +
( )210,σ∼ N
( )20,σΔ∼ N( )210,σ∼ N
+1W
2W 2nX
1nX
23
Communication Systems Laboratory
Degraded Binary Symmetric Broadcast Channel
– Channel Model
– Optimal Transmission Strategy Optimal Transmission Strategy [Cover72][Bergmans73]
45
X2Y
1Y
NΔ1N
1N
XOR
XOR XOR
XOR
XOR XOR
Successive Decoder
Decoder 2
1W
2W
nX
2nY
1nY
nNΔ1nN
1nN
XOR
1W
2W 2nX
1nX
Communication Systems Laboratory
Broadcast Z Channels• Broadcast Z Channels
• Broadcast Z channels are stochastically degraded broadcast channels.
46
XY1
Y2
1
0
1
0
1
0
1α
2α 1 20 1α α< < <
X Y1
1α
Y2
αΔ2 1
11α αα
αΔ
−=
−
24
Communication Systems Laboratory
Degraded Z Broadcast Channel
– Channel Model
– Optimal Transmission Strategy
47
1 1Pr( 1)N α= =
Pr( 1)N αΔ Δ= =X2Y
1Y
NΔ1N
1N
OR
OR OR
1 1Pr( 1)N α= =
OR
OR OR
Successive Decoder
Decoder 2
1W
2W
nX
2nY
1nY
nNΔ1nN
1nN
OR
1W
2W 2nX
1nX
– Channel Model
– Optimal Transmission Strategy[Xie07]
Communication Systems Laboratory
Proving the Optimal Transmission Strategy
All rate pairs on the boundary of the capacity region can be achieved with the following strategy:
48
X Y1
1α
Y2
αΔ
X2
1p1q2q
2pγ
0,γ =
1 1 1(1 ) (1 )1
1 1,(1 )( 1)H q
e α αα − − ≤ ≤− +
2 1 2 1 21 2 1 2 1 1 1 1
2 1 2 1 1
1 (1 ) log(1 (1 ))( (1 )) (1 )log ( ( (1 )) (1 )).(1 ) log(1 (1 ))
q q qH q q H q q Hq q q
α αα α α αα α
− − − −− − − = − − −
− − −
25
Communication Systems Laboratory
A class of degraded broadcast channels
• function-like component channels
• have the same alphabet. • The channel function is commutative.• The channel function is associative.
The Department of Electrical Engineering UCLA 49
X2Y
1Y
NΔ1N
1N
f
f f
1 1 2, , , ,X N N Y YΔ
Communication Systems Laboratory
A Conjecture• We believe that the optimal transmission
strategies for this class of degraded broadcast channels are independent encoding schemes.
The Department of Electrical Engineering UCLA 50
f
f f
Successive Decoder
Decoder 2
1W
2W
nX
2nY
1nY
nNΔ1nN
1nN
f1W
2W 2nX
1nX
26
Communication Systems Laboratory
Explicit Broadcast Z Channel Capacity Region
– The boundary of the capacity region is
where parameters satisfy
51
1 2 1 1 2 1 1
2 2 1 2 2 1 2
( (1 )) ((1 ))( (1 )) ( (1 ))
R q H q q q HR H q q q H q
α αα α
= − − −⎧⎨ = − − −⎩
1 1 1(1 ) /(1 )1
1 1,(1 )( 1)H q
e α αα − − ≤ ≤− +
1 2,q q
2 1 2 1 21 2 1 2 1 1 1 1
2 1 2 1 1
1 (1 ) log(1 (1 ))( (1 )) (1 )log ( ( (1 )) (1 )).(1 ) log(1 (1 ))
q q qH q q H q q Hq q q
α αα α α αα α
− − − −− − − = − − −
− − −
Communication Systems Laboratory
Z-channel Successive Decoder• Decoder structure of the successive decoder
for user 1
52
1 21 1 2
2
ˆif 0ˆ( , )
ˆif 1y x
y e y xerasure x
=⎧= = ⎨ =⎩
27
Communication Systems Laboratory
Nonlinear Turbo Codes• Nonlinear turbo codes can provide a
controlled distribution of ones and zeros.• Nonlinear turbo codes designed for Z
channels are used. [Griot06]
• Encoding structure of nonlinear turbo codes:
53
Communication Systems Laboratory
Simulation Results
54
The cross probabilities of the broadcast Z channel are
The simulated rates are very close to the capacity region.
Only 0.04 bits or less away from optimal rates in R1.
Only 0.02 bits or less away from optimal rates in R2.
1 20.15, 0.6.α α= =
28
Communication Systems Laboratory
References• [Cover98] T. M. Cover, “Comments on broadcast channels,”
IEEE Trans. Inform. Theory, vol. IT-44, pp. 2524-2530, 1998• [Cover75] T. M. Cover, “An achievable rate region for the
broadcast channel,” IEEE Trans. Inform. Theory, vol. IT-21 ,pp. 399-404, 1975
• [Hajek79] B. E. Hajek & M. B. Pursley, “Evaluation of an achievable rate region for the broadcast channel,” IEEE Trans. Inform. Theory, vol. IT-25 ,pp. 36-46, 1979
• [Gallager74] R. G. Gallager, “Capacity and coding for degraded broadcast channels,” Probl. Pered. Inform., vol. 10, no. 3, pp. 3–14, July–Sept. 1974; translated in Probl. Inform. Transm., pp. 185–193, July–Sept. 1974.
• [Benzel79] R. Benzel, “The capacity region of a class of discrete additive degraded interference channels,” IEEE Trans. Inform. Theory, vol. IT-25, pp. 228–231, Mar. 1979.
The Department of Electrical Engineering UCLA 55
Communication Systems Laboratory
References• [Sato78] H. Sato, “An outer bound to the capacity region of
broadcast channels,” IEEE Trans. Inform. Theory, vol. IT-24 ,pp. 374-377, 1978.
• [VAN75] E. van der Meulen, “Random coding theorems for the general discrete memoryless broadcast channel,” IEEE Trans. Inform. Theory, vol. IT-21, pp. 180-190, 1975.
• [Marton79] K. Marton, “A coding theorem for the discrete memoryless broadcast channel,” IEEE Trans. Inform. Theory, vol. IT-25, pp. 306–311,1979.
• [Cover72] T. M. Cover, “Broadcast channels,” IEEE Trans. Inform. Theory, vol. IT-18, pp. 2–14, Jan. 1972.
• [Bergmans73] P. P. Bergmans, “Random coding theorem for broadcast channels with degraded components,” IEEE Trans. Inform. Theory, vol. IT-19, pp. 197–207, Mar. 1973.
The Department of Electrical Engineering UCLA 56
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Communication Systems Laboratory
References• [Bergmans74] P. P. Bergmans, “A simple converse for
broadcast channels with additive white Gaussian noise,” IEEE Trans. Inform. Theory, vol. IT-20, pp. 279–280, Mar. 1974.
• [Griot06] M.Griot, A. I. Vila Casado and R. D. Wesel, "Non-linear Turbo Codes for Interleaver-Division Multiple Access on the OR Channel". Globecom 2006, 27 Nov. - 1 Dec., San Francisco, USA.
• [Xie07] B. Xie, M. Griot, A. I. Vila Casado and R. D. Wesel, "Optimal Transmission Strategy and Capacity Region for Broadcast Z Channels", IEEE Information Theory Workshop 2007.
The Department of Electrical Engineering UCLA 57