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Continuous-Time Fourier Transform
Hongkai Xiong 熊红凯
http://min.sjtu.edu.cn
Department of Electronic Engineering Shanghai Jiao Tong University
𝑥𝑥𝑘𝑘[𝑛𝑛] → 𝑦𝑦𝑘𝑘[𝑛𝑛] ⟹ � 𝑎𝑎𝑘𝑘𝑥𝑥𝑘𝑘[𝑛𝑛]𝑘𝑘 → ∑ 𝑎𝑎𝑘𝑘𝑘𝑘 𝑦𝑦𝑘𝑘[𝑛𝑛]
• If we can find a set of “basic” signals, such that ▫ a rich class of signals can be represented as linear
combinations of these basic (building block) signals. ▫ the response of LTI Systems to these basic signals are both
simple and insightful
• Candidate sets of “basic” signals ▫ Unit impulse function and its delays: 𝛿𝛿(𝑡𝑡)/𝛿𝛿[𝑛𝑛] ▫ Complex exponential/sinusoid signals: 𝑒𝑒𝑠𝑠𝑡𝑡 , 𝑒𝑒𝑗𝑗𝑗𝑗𝑗/𝑧𝑧𝑛𝑛, 𝑒𝑒𝑗𝑗𝑗𝑗𝑛𝑛
LTI Systems
2
Fourier Series of CT Periodic Signals • Recall a periodic CT signal 𝑥𝑥 𝑡𝑡 ▫ with fundamental period 𝑇𝑇, and ▫ fundamental frequency 𝜔𝜔0 = 2𝜋𝜋/𝑇𝑇
• Fourier series represent 𝑥𝑥 𝑡𝑡 in terms of harmonically related complex exponentials ▫ Synthesis equation
𝑥𝑥 𝑡𝑡 = � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
= � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘(2𝜋𝜋/𝑇𝑇)𝑡𝑡∞
𝑘𝑘=−∞
▫ Analysis equation
𝑎𝑎𝑘𝑘 =1𝑇𝑇�𝑥𝑥 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡 𝑑𝑑𝑡𝑡𝑇𝑇
=1𝑇𝑇�𝑥𝑥 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑘𝑘(2𝜋𝜋/𝑇𝑇)𝑡𝑡 𝑑𝑑𝑡𝑡𝑇𝑇
3
• In one period, 𝑥𝑥𝑇𝑇 𝑡𝑡 = �1, 𝑡𝑡 < 𝑇𝑇1 0, 𝑇𝑇1 < 𝑡𝑡 < 𝑇𝑇/2
• Fourier coefficients
𝑎𝑎0=1𝑇𝑇� 1𝑇𝑇1
−𝑇𝑇1𝑑𝑑𝑡𝑡 =
2𝑇𝑇1𝑇𝑇
, 𝑎𝑎𝑘𝑘 =1𝑇𝑇� 𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇1
−𝑇𝑇1=
2sin (𝑘𝑘𝜔𝜔0𝑇𝑇1)𝑘𝑘𝜔𝜔0𝑇𝑇
, 𝑘𝑘 ≠ 0
• Frequency component at 𝜔𝜔𝑘𝑘 = 𝑘𝑘𝜔𝜔0 satisfies
𝑇𝑇𝑎𝑎𝑘𝑘 =2 sin 𝜔𝜔𝑇𝑇1
𝜔𝜔�𝑗𝑗=𝑘𝑘𝑗𝑗0
𝑇𝑇𝑎𝑎𝑘𝑘 thought as sampled value of envelope 𝑋𝑋 𝑗𝑗𝜔𝜔 ≜ 2 sin(𝜔𝜔𝑇𝑇1)/𝜔𝜔 at 𝜔𝜔𝑘𝑘 = 𝑘𝑘𝜔𝜔0
Motivating Example: Periodic Square Wave
4
• 𝑋𝑋 𝑗𝑗𝜔𝜔𝑘𝑘 ≜ 2 sin(𝜔𝜔𝑘𝑘𝑇𝑇1)/𝜔𝜔𝑘𝑘 for fixed 𝑇𝑇1 and increasing 𝑇𝑇
• Observation: as 𝑇𝑇 → ∞, discrete frequencies sampled more densely
Motivating Example: Periodic Square Wave
5
• As 𝑻𝑻 → ∞, 𝒙𝒙𝑻𝑻 𝒕𝒕 → 𝒙𝒙 𝒕𝒕 ≜ 𝒖𝒖 𝒕𝒕 + 𝑻𝑻𝟏𝟏𝟐𝟐
− 𝒖𝒖(𝒕𝒕 − 𝑻𝑻𝟏𝟏𝟐𝟐
), a rectangular impulse
𝑥𝑥𝑇𝑇 𝑡𝑡 = � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
=1𝑇𝑇� 𝑋𝑋(𝑗𝑗𝑘𝑘𝜔𝜔0)𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
=12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
⟹ lim𝑇𝑇→∞
𝑥𝑥𝑇𝑇 𝑡𝑡 =12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞
• Thus
𝑥𝑥(𝑡𝑡) =12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞
Motivating Example: Periodic Square Wave
6
• For envelope 𝑿𝑿(𝒋𝒋𝒋𝒋)
𝑋𝑋 𝑗𝑗𝜔𝜔𝑘𝑘 = 𝑇𝑇𝑎𝑎𝑘𝑘
= � 𝑥𝑥𝑇𝑇(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇2
−𝑇𝑇2
= � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑘𝑘𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇2
−𝑇𝑇2
= � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑘𝑘𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
• Thus
𝑋𝑋(𝑗𝑗𝜔𝜔) = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
Motivating Example: Periodic Square Wave
7
CT Fourier Transform of Aperiodic Signal 𝒙𝒙(𝒕𝒕)
• General strategy ▫ approximate 𝑥𝑥 𝑡𝑡 by a periodic signal 𝑥𝑥𝑇𝑇 𝑡𝑡 with infinite period 𝑇𝑇
9
𝑥𝑥 𝑡𝑡
−𝑇𝑇1 0 𝑇𝑇1
⟹ lim𝑇𝑇→∞
𝑥𝑥𝑇𝑇 𝑡𝑡 = 𝑥𝑥(𝑡𝑡) 𝑥𝑥𝑇𝑇 𝑡𝑡
−𝑇𝑇 − 𝑇𝑇2
− 𝑇𝑇1 0 𝑇𝑇1 𝑇𝑇2
𝑇𝑇
⋯ ⋯
CT Fourier Transform of Aperiodic Signal 𝒙𝒙(𝒕𝒕)
• Step 1: for aperiodic signal 𝑥𝑥 𝑡𝑡 with sup 𝑥𝑥 𝑡𝑡 ⊂ [−𝑇𝑇1,𝑇𝑇1] construct a periodic signal 𝑥𝑥𝑇𝑇 𝑡𝑡 , for which one period is 𝑥𝑥 𝑡𝑡
𝑥𝑥𝑇𝑇 𝑡𝑡 = � 𝑥𝑥(𝑡𝑡 − 𝑘𝑘𝑇𝑇)∞
𝑘𝑘=−∞
▫ Then 𝑥𝑥 𝑡𝑡 = 𝑥𝑥𝑇𝑇 𝑡𝑡 ,∀ 𝑡𝑡 < 𝑇𝑇/2
10
𝑥𝑥𝑇𝑇 𝑡𝑡
⋯ ⋯
𝑥𝑥 𝑡𝑡
−𝑇𝑇 − 𝑇𝑇2
− 𝑇𝑇1 0 𝑇𝑇1 𝑇𝑇2
𝑇𝑇
CT Fourier Transform of Aperiodic Signal 𝒙𝒙(𝒕𝒕)
• Step 2: determine the Fourier series representation for 𝑥𝑥𝑇𝑇 𝑡𝑡 ▫ Fourier series coefficients
𝑎𝑎𝑘𝑘 =1𝑇𝑇� 𝑥𝑥𝑇𝑇(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇/2
−𝑇𝑇/2=
1𝑇𝑇� 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
▫ Define the envelope of 𝑇𝑇𝑎𝑎𝑘𝑘
𝑋𝑋(𝑗𝑗𝜔𝜔) = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
▫ Then
𝑥𝑥𝑇𝑇 𝑡𝑡 = � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
=1𝑇𝑇 � 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡 =
∞
𝑘𝑘=−∞
12𝜋𝜋 � 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
11
𝑥𝑥𝑇𝑇 𝑡𝑡
⋯ ⋯
𝑥𝑥 𝑡𝑡
−𝑇𝑇 − 𝑇𝑇2
− 𝑇𝑇1 0 𝑇𝑇1 𝑇𝑇2
𝑇𝑇
CT Fourier Transform of Aperiodic Signal 𝒙𝒙(𝒕𝒕)
• Step 3: approximate 𝑥𝑥 𝑡𝑡 with 𝑥𝑥𝑇𝑇 𝑡𝑡 by increasing 𝑇𝑇 → ∞
▫ As 𝑇𝑇 → ∞ ⟹𝜔𝜔0 → 0, 𝑥𝑥𝑇𝑇 𝑡𝑡 → 𝑥𝑥 𝑡𝑡 ,𝜔𝜔0 → 𝑑𝑑𝜔𝜔,∑ → ∫
𝑥𝑥𝑇𝑇 𝑡𝑡 =12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
⇓
𝑥𝑥 𝑡𝑡 = lim𝑇𝑇→∞
𝑥𝑥𝑇𝑇(𝑡𝑡) = lim𝑗𝑗0→0
12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
=12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞
12
𝑥𝑥𝑇𝑇 𝑡𝑡
⋯ ⋯
𝑥𝑥 𝑡𝑡
−𝑇𝑇 − 𝑇𝑇2
− 𝑇𝑇1 0 𝑇𝑇1 𝑇𝑇2
𝑇𝑇
CT Fourier Transform Pair • Fourier transform (analysis equation)
𝑋𝑋 𝑗𝑗𝜔𝜔 = ℱ{𝑥𝑥(𝑡𝑡)} = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
where 𝑋𝑋 𝑗𝑗𝜔𝜔 called spectrum of 𝑥𝑥(𝑡𝑡)
• Inverse Fourier transform (synthesis equation)
𝑥𝑥 𝑡𝑡 = ℱ−1{𝑋𝑋(𝑗𝑗𝜔𝜔)} =12𝜋𝜋� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞
Superposition of complex exponentials at continuum of frequencies, frequency component 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡 has “amplitude” of 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑑𝑑𝜔𝜔/2𝜋𝜋
13
CT Fourier Series of Periodic Signal 𝒙𝒙𝑻𝑻(𝒕𝒕)
• Fourier Transform of a finite duration signal 𝑥𝑥 𝑡𝑡 that is equal to 𝑥𝑥𝑇𝑇 𝑡𝑡 over one period, e.g., for 𝑡𝑡0 ≤ 𝑡𝑡 ≤ 𝑡𝑡0 + 𝑇𝑇
𝑋𝑋 𝑗𝑗𝜔𝜔 = ℱ{𝑥𝑥(𝑡𝑡)} = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
• Fourier coefficients of periodic signal 𝑥𝑥𝑇𝑇 𝑡𝑡 with period 𝑇𝑇
𝑎𝑎𝑘𝑘 =1𝑇𝑇� 𝑥𝑥𝑇𝑇 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡 =
1𝑇𝑇� 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡
𝑡𝑡0+𝑇𝑇
𝑡𝑡0
𝑡𝑡0+𝑇𝑇
𝑡𝑡0
=1𝑇𝑇� 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞=
1𝑇𝑇𝑋𝑋(𝑗𝑗𝜔𝜔)�
𝑗𝑗=𝑘𝑘𝑗𝑗0
⟹ proportional to samples of the Fourier transform of 𝑥𝑥 𝑡𝑡 , i.e., one period of 𝑥𝑥𝑇𝑇 𝑡𝑡
14
Convergence of Fourier Transform • Suppose from 𝑥𝑥(𝑡𝑡), we have
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
• Let 𝑥𝑥�(𝑡𝑡) be the Fourier transform representation of 𝑥𝑥(𝑡𝑡),
obtained using the synthesis equation
𝑥𝑥�(𝑡𝑡) =12𝜋𝜋� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞
• Question: when can 𝑥𝑥�(𝑡𝑡) be a valid representation of the original
signal 𝑥𝑥(𝑡𝑡)?
15
Finite Energy Condition • One useful notion for engineers: ▫ no energy in approximation error
𝑒𝑒 𝑡𝑡 ≜ 𝑥𝑥 𝑡𝑡 − 𝑥𝑥� 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 −12𝜋𝜋� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞
and � 𝑒𝑒(𝑡𝑡) 2𝑑𝑑𝑡𝑡 = 0∞
−∞
• Finite energy condition (square integrable)
� 𝑥𝑥(𝑡𝑡) 2𝑑𝑑𝑡𝑡 < ∞∞
−∞
▫ Note: does not guarantee 𝑥𝑥(𝑡𝑡) equal to its Fourier representation at any time 𝑡𝑡, but guarantees no energy in approximation error
16
• Condition 1. ▫ 𝑥𝑥(𝑡𝑡) is absolutely integrable, i.e.,
� |𝑥𝑥 𝑡𝑡 |𝑑𝑑𝑡𝑡∞
−∞< ∞
• Condition 2. ▫ Within any finite interval, 𝑥𝑥(𝑡𝑡) has a finite number of maxima
and minima
• Condition 3. ▫ Within any finite interval, 𝑥𝑥(𝑡𝑡) has only a finite number of
discontinuities with finite values
• ⟹ absolutely integrable signals that are continuous or with a finite number of discontinuities have Fourier transforms
Dirichlet Conditions
17
Example: Right-sided Decaying Exponential
• 𝑥𝑥 𝑡𝑡 = 𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢 𝑡𝑡 ,𝑎𝑎 > 0 is a real number
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞= � 𝑒𝑒−𝑎𝑎𝑡𝑡𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡
∞
0
= −1
𝑎𝑎 + 𝑗𝑗𝜔𝜔𝑒𝑒−(𝑎𝑎+𝑗𝑗𝑗𝑗)𝑡𝑡�
0
∞
=1
𝑎𝑎 + 𝑗𝑗𝜔𝜔
𝑋𝑋 𝑗𝑗𝜔𝜔 =1
𝑎𝑎2 + 𝜔𝜔2, arg𝑋𝑋 𝑗𝑗𝜔𝜔 = − arctan
𝜔𝜔𝑎𝑎
• Observation: ▫ Magnitude spectrum: even symmetry ▫ Phase spectrum: odd symmetry
• Note: also works for complex 𝑎𝑎 with ℛℯ 𝑎𝑎 > 0
18
Example: Two-sided Decaying Exponential
• 𝑥𝑥 𝑡𝑡 = 𝑒𝑒−|𝑎𝑎|𝑡𝑡𝑢𝑢 𝑡𝑡 ,𝑎𝑎 > 0 is a real number
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
= � 𝑒𝑒−|𝑎𝑎|𝑡𝑡𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡∞
−∞
= � 𝑒𝑒𝑎𝑎𝑡𝑡𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡0
−∞+ � 𝑒𝑒−𝑎𝑎𝑡𝑡𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡
∞
0
=1
𝑎𝑎 − 𝑗𝑗𝜔𝜔𝑒𝑒(𝑎𝑎−𝑗𝑗𝑗𝑗)𝑡𝑡�
−∞
0
−1
𝑎𝑎 + 𝑗𝑗𝜔𝜔𝑒𝑒−(𝑎𝑎+𝑗𝑗𝑗𝑗)𝑡𝑡�
0
∞
=1
𝑎𝑎 − 𝑗𝑗𝜔𝜔+
1𝑎𝑎 + 𝑗𝑗𝜔𝜔
=2𝑎𝑎
𝑎𝑎2 + 𝜔𝜔2
• Note: also works for complex 𝑎𝑎 with ℛℯ 𝑎𝑎 > 0
19
Example: Rectangular Pulse • 𝑥𝑥 𝑡𝑡 = 𝑢𝑢 𝑡𝑡 + 𝑇𝑇1 − 𝑢𝑢(𝑡𝑡 − 𝑇𝑇1)
• Fourier transform
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇1
−𝑇𝑇1= 2
sin(𝜔𝜔𝑇𝑇1)𝜔𝜔
• Inverse Fourier transform
𝑥𝑥� 𝑡𝑡 =12𝜋𝜋
� 2sin(𝜔𝜔𝑇𝑇1)
𝜔𝜔𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞
• As 𝑇𝑇1 → ∞, (define sinc 𝜃𝜃 = sin(𝜋𝜋𝜋𝜋)𝜋𝜋𝜋𝜋
)
▫ Frequency domain: 2𝜋𝜋 sin(𝑗𝑗𝑇𝑇1)𝜋𝜋𝑗𝑗
= 2𝜋𝜋 𝑇𝑇1𝜋𝜋
sinc 𝑗𝑗𝑇𝑇1𝜋𝜋
→ 2𝜋𝜋𝛿𝛿(𝜔𝜔)
▫ Time domain: 𝑥𝑥 𝑡𝑡 → 1, DC
20
1 1
1
1
Example: Ideal Lowpass Filter • Frequency response 𝐻𝐻(𝑗𝑗𝜔𝜔) = 𝑢𝑢 𝜔𝜔 + 𝜔𝜔𝑐𝑐 − 𝑢𝑢(𝜔𝜔 − 𝜔𝜔𝑐𝑐)
• Impulse response
ℎ 𝑡𝑡 =12𝜋𝜋
� 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔𝑗𝑗𝑐𝑐
−𝑗𝑗𝑐𝑐
=sin(𝜔𝜔𝑐𝑐 𝑡𝑡)
𝜋𝜋𝑡𝑡=𝜔𝜔𝑐𝑐𝜋𝜋
sinc𝜔𝜔𝑐𝑐𝑡𝑡𝜋𝜋
• As 𝜔𝜔𝑐𝑐 → ∞, ▫ Time domain ℎ 𝑡𝑡 → 𝛿𝛿(𝑡𝑡), becomes identity system
▫ Frequency domain 𝐻𝐻(𝑗𝑗𝜔𝜔) → 1, passes all frequencies
21
Examples • Unit impulse 𝑥𝑥 𝑡𝑡 = 𝛿𝛿 𝑡𝑡
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝛿𝛿(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡+∞
−∞= 1
𝑥𝑥 𝑡𝑡 =12𝜋𝜋� 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞= lim
𝑗𝑗𝑐𝑐→∞
12𝜋𝜋� 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
𝑗𝑗𝑐𝑐
−𝑗𝑗𝑐𝑐
= lim𝑗𝑗𝑐𝑐→∞
sin(𝜔𝜔𝑐𝑐 𝑡𝑡)𝜋𝜋𝑡𝑡 = 𝛿𝛿(𝑡𝑡)
𝜹𝜹(𝒕𝒕) has “white” spectrum, equal amount of all frequencies!
• DC Signal 𝑥𝑥(𝑡𝑡) = 1
𝑋𝑋 𝑗𝑗𝜔𝜔 = lim𝑇𝑇1→∞
� 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇1
−𝑇𝑇1= lim
𝑇𝑇1→∞2𝜋𝜋
sin(𝜔𝜔𝑇𝑇1)𝜋𝜋𝜔𝜔 = 2𝜋𝜋𝛿𝛿(𝜔𝜔)
𝑥𝑥 𝑡𝑡 =12𝜋𝜋� 𝑋𝑋(𝑗𝑗𝜔𝜔)𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞=
12𝜋𝜋� 2𝜋𝜋𝛿𝛿(𝜔𝜔)𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔 = 1
∞
−∞
Spectrum of DC signal is impulse at zero frequency!
23
Fourier Transform of Periodic Signals • A periodic signal 𝑥𝑥 𝑡𝑡 with fundamental frequency 𝜔𝜔0 =2𝜋𝜋/𝑇𝑇 has a Fourier series representation
𝑥𝑥 𝑡𝑡 = � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
⟹ 𝑋𝑋 𝑗𝑗𝜔𝜔 = ℱ{𝑥𝑥 𝑡𝑡 } = � 𝑎𝑎𝑘𝑘ℱ{𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡}∞
𝑘𝑘=−∞
• Question then becomes
ℱ{𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡} =?
24
Fourier Transform of Periodic Signals • Using the basic Fourier transform pair
𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 ℱ
2𝜋𝜋𝛿𝛿 𝜔𝜔 − 𝜔𝜔0
▫ ℱ{𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡} = lim𝑇𝑇1→∞
∫ 𝑒𝑒−𝑗𝑗 𝑗𝑗−𝑗𝑗0 𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇1−𝑇𝑇1
= lim𝑇𝑇1→∞
2𝜋𝜋 sin[(𝑗𝑗−𝑗𝑗0)𝑇𝑇1]𝜋𝜋 𝑗𝑗−𝑗𝑗0
= 2𝜋𝜋𝛿𝛿(𝜔𝜔 − 𝜔𝜔0)
▫ ℱ−1{2𝜋𝜋𝛿𝛿(𝜔𝜔 − 𝜔𝜔0)} = 12𝜋𝜋 ∫ 2𝜋𝜋𝛿𝛿 𝜔𝜔 − 𝜔𝜔0 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞−∞ = 𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡
• Thus, the Fourier transform of periodic signal 𝑥𝑥(𝑡𝑡) is
𝑋𝑋 𝑗𝑗𝜔𝜔 = ℱ{𝑥𝑥 𝑡𝑡 } = � 𝑎𝑎𝑘𝑘ℱ{𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡}∞
𝑘𝑘=−∞
= � 2𝜋𝜋𝑎𝑎𝑘𝑘𝛿𝛿(𝜔𝜔 − 𝑘𝑘𝜔𝜔0)∞
𝑘𝑘=−∞
25
Fourier Transform of Periodic Signals • A periodic signal 𝑥𝑥 𝑡𝑡 with fundamental frequency 𝜔𝜔0 = 2𝜋𝜋/𝑇𝑇
• Fourier series
𝑥𝑥 𝑡𝑡 = � 𝑎𝑎𝑘𝑘𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡∞
𝑘𝑘=−∞
𝑎𝑎𝑘𝑘 =1𝑇𝑇� 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇2
−𝑇𝑇2
• Fourier transform
𝑥𝑥(𝑡𝑡) ℱ
𝑋𝑋(𝑗𝑗𝜔𝜔) = � 2𝜋𝜋𝑎𝑎𝑘𝑘𝛿𝛿(𝜔𝜔 − 𝑘𝑘𝜔𝜔0)∞
𝑘𝑘=−∞
▫ Spectrum of periodic signal consists of a impulse train occurring at harmonically related frequencies!
▫ Areas of impulses are 𝟐𝟐𝟐𝟐 times Fourier series coefficients
26
Example: Cosine and Sine • 𝑥𝑥𝑐𝑐(𝑡𝑡) = cos(𝜔𝜔0𝑡𝑡) = 1
2𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 + 1
2𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡
⟹ 𝑎𝑎1= 1,𝑎𝑎−1 = 1, 𝑎𝑎𝑘𝑘 = 0,𝑘𝑘 ≠ ±1
⟹ 𝑋𝑋𝑐𝑐(𝑗𝑗𝜔𝜔) = 𝜋𝜋[𝛿𝛿(𝜔𝜔 − 𝜔𝜔0) + 𝛿𝛿(𝜔𝜔 + 𝜔𝜔0)]
• 𝑥𝑥𝑠𝑠(𝑡𝑡) = sin(𝜔𝜔0𝑡𝑡) = 12𝑗𝑗𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 − 1
2𝑗𝑗𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡
⟹ 𝑎𝑎1= 12𝑗𝑗
,𝑎𝑎−1 = − 12𝑗𝑗
, 𝑎𝑎𝑘𝑘 = 0,𝑘𝑘 ≠ ±1
⟹ 𝑋𝑋𝑠𝑠 𝑗𝑗𝜔𝜔 =𝜋𝜋𝑗𝑗𝛿𝛿 𝜔𝜔 − 𝜔𝜔0 −
𝜋𝜋𝑗𝑗𝛿𝛿(𝜔𝜔 + 𝜔𝜔0)
27
Example: Periodic Square Wave
𝑎𝑎0=1𝑇𝑇� 1𝑇𝑇1
−𝑇𝑇1𝑑𝑑𝑡𝑡 =
2𝑇𝑇1𝑇𝑇
, 𝑎𝑎𝑘𝑘 =1𝑇𝑇� 𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡𝑇𝑇1
−𝑇𝑇1=
2sin (𝑘𝑘𝜔𝜔0𝑇𝑇1)𝑘𝑘𝜔𝜔0𝑇𝑇
, 𝑘𝑘 ≠ 0
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 2𝜋𝜋2 sin 𝑘𝑘𝜔𝜔0𝑇𝑇1
𝑘𝑘𝜔𝜔0𝑇𝑇
∞
𝑘𝑘=−∞
𝛿𝛿 𝜔𝜔 − 𝑘𝑘𝜔𝜔0 = �2 sin 𝑘𝑘𝜔𝜔0𝑇𝑇1
𝑘𝑘
∞
𝑘𝑘=−∞
𝛿𝛿 𝜔𝜔 − 𝑘𝑘𝜔𝜔0
28
Example: Periodic Impulse Train • 𝑥𝑥(𝑡𝑡) = ∑ 𝛿𝛿(𝑡𝑡 − 𝑘𝑘𝑇𝑇)∞
𝑘𝑘=−∞
⟹ 𝑎𝑎𝑘𝑘=1𝑇𝑇� 𝑥𝑥 𝑡𝑡𝑇𝑇2
−𝑇𝑇2
𝑒𝑒−𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝑑𝑑𝑡𝑡 =1𝑇𝑇
⟹ 𝑋𝑋 𝑗𝑗𝜔𝜔 = �2𝜋𝜋𝑇𝑇𝛿𝛿(𝜔𝜔 − 𝑘𝑘
2𝜋𝜋𝑇𝑇
)∞
𝑘𝑘=−∞
29
Properties of CT Fourier Transform
𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 𝑦𝑦(𝑡𝑡) ℱ
𝑌𝑌(𝑗𝑗𝜔𝜔)
• Linearity
𝑎𝑎𝑥𝑥(𝑡𝑡) + 𝑏𝑏𝑦𝑦(𝑡𝑡) ℱ
𝑎𝑎𝑋𝑋(𝑗𝑗𝜔𝜔) + 𝑏𝑏𝑌𝑌(𝑗𝑗𝜔𝜔)
• Time shifting
𝑥𝑥(𝑡𝑡 − 𝑡𝑡0) ℱ
𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡0𝑋𝑋(𝑗𝑗𝜔𝜔) • Frequency shifting
𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡𝑥𝑥(𝑡𝑡) ℱ
𝑋𝑋(𝑗𝑗 𝜔𝜔 − 𝜔𝜔0 )
30
Example: Multipath Fading Effect Transmitter: 𝑥𝑥 𝑡𝑡 Receiver: 𝑦𝑦 𝑡𝑡 = 𝑎𝑎0𝑥𝑥 𝑡𝑡 + 𝑎𝑎1𝑥𝑥(𝑡𝑡 − 𝜏𝜏)
• 𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑎𝑎0𝑋𝑋 𝑗𝑗𝜔𝜔 + 𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗𝑎𝑎1𝑋𝑋 𝑗𝑗𝜔𝜔 = (𝑎𝑎0 + 𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗𝑎𝑎1)𝑋𝑋 𝑗𝑗𝜔𝜔 • Let 𝑥𝑥 𝑡𝑡 = 𝑢𝑢 𝑡𝑡 + 𝑇𝑇 − 𝑢𝑢 𝑡𝑡 − 𝑇𝑇
𝑋𝑋 𝑗𝑗𝜔𝜔 =2 sin(𝜔𝜔𝑇𝑇)
𝜔𝜔
𝑌𝑌 𝑗𝑗𝜔𝜔 = (𝑎𝑎0 + 𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗𝑎𝑎1)2 sin(𝜔𝜔𝑇𝑇)
𝜔𝜔
• When 𝑎𝑎0 = 𝑎𝑎1 = 1
𝑌𝑌 𝑗𝑗𝜔𝜔 = 4𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗/2 cos 𝜔𝜔𝜏𝜏/22 sin(𝜔𝜔𝑇𝑇)
𝜔𝜔
31
Example: Modulation Baseband signal: 𝑥𝑥 𝑡𝑡 Modulated signal: 𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 cos(𝜔𝜔𝑐𝑐𝑡𝑡)
• 𝑦𝑦 𝑡𝑡 = 12𝑥𝑥(𝑡𝑡)(𝑒𝑒𝑗𝑗𝑗𝑗𝑐𝑐𝑡𝑡 + 𝑒𝑒−𝑗𝑗𝑗𝑗𝑐𝑐𝑡𝑡 )
𝑌𝑌 𝑗𝑗𝜔𝜔 =12𝑋𝑋 𝑗𝑗(𝜔𝜔 − 𝜔𝜔𝑐𝑐 +
12𝑋𝑋 𝑗𝑗(𝜔𝜔 + 𝜔𝜔𝑐𝑐
• Let 𝑥𝑥 𝑡𝑡 = 𝑢𝑢 𝑡𝑡 + 𝑇𝑇 − 𝑢𝑢 𝑡𝑡 − 𝑇𝑇
𝑌𝑌 𝑗𝑗𝜔𝜔 =sin((𝜔𝜔 − 𝜔𝜔𝑐𝑐)𝑇𝑇)
𝜔𝜔 − 𝜔𝜔𝑐𝑐+
sin((𝜔𝜔 + 𝜔𝜔𝑐𝑐)𝑇𝑇)𝜔𝜔 + 𝜔𝜔𝑐𝑐
32
Properties of CT Fourier Transform • Time reversal
𝑥𝑥(−𝑡𝑡) ℱ
𝑋𝑋(−𝑗𝑗𝜔𝜔)
• Conjugation
𝑥𝑥∗ 𝑡𝑡 ℱ
𝑋𝑋∗ −𝑗𝑗𝜔𝜔
Proof: ℱ 𝑥𝑥∗ 𝑡𝑡 = ∫ 𝑥𝑥∗ 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 =+∞−∞ ∫ 𝑥𝑥 𝑡𝑡 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡+∞
−∞
∗= 𝑋𝑋∗ (−𝑗𝑗𝜔𝜔)
• Conjugate Symmetry ▫ 𝑥𝑥 𝑡𝑡 real ⟺ 𝑋𝑋(−𝑗𝑗𝜔𝜔) = 𝑋𝑋∗(𝑗𝑗𝜔𝜔) ▫ 𝑥𝑥 𝑡𝑡 even ⟺ 𝑋𝑋(𝑗𝑗𝜔𝜔) even, 𝑥𝑥 𝑡𝑡 odd ⟺ 𝑋𝑋(𝑗𝑗𝜔𝜔) odd ▫ 𝑥𝑥 𝑡𝑡 real and even ⟺ 𝑋𝑋(𝑗𝑗𝜔𝜔) real and even ▫ 𝑥𝑥 𝑡𝑡 real and odd ⟺ 𝑋𝑋(𝑗𝑗𝜔𝜔) purely imaginary and odd
33
• For a real signal: 𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋(𝑗𝑗𝜔𝜔)
𝑥𝑥𝑒𝑒 𝑡𝑡 =12 𝑥𝑥 𝑡𝑡 + 𝑥𝑥 −𝑡𝑡
ℱ ℛℯ{𝑋𝑋(𝑗𝑗𝜔𝜔)}
𝑥𝑥𝑜𝑜 𝑡𝑡 =12 𝑥𝑥 𝑡𝑡 − 𝑥𝑥 −𝑡𝑡
ℱ 𝑗𝑗 ⋅ ℐ𝓂𝓂{𝑋𝑋(𝑗𝑗𝜔𝜔)}
• Proof: ▫ Since 𝑥𝑥 𝑡𝑡 is real, then 𝑋𝑋(𝑗𝑗𝜔𝜔) is conjugate symmetric
ℱ 𝑥𝑥𝑒𝑒 𝑡𝑡 =12𝑋𝑋(𝑗𝑗𝜔𝜔) + 𝑋𝑋(−𝑗𝑗𝜔𝜔) =
12𝑋𝑋(𝑗𝑗𝜔𝜔) + 𝑋𝑋∗(𝑗𝑗𝜔𝜔) = ℛℯ 𝑋𝑋(𝑗𝑗𝜔𝜔)
ℱ 𝑥𝑥𝑜𝑜 𝑡𝑡 =12𝑋𝑋 𝑗𝑗𝜔𝜔 − 𝑋𝑋(−𝑗𝑗𝜔𝜔) =
12𝑋𝑋 𝑗𝑗𝜔𝜔 − 𝑋𝑋∗(𝑗𝑗𝜔𝜔) = 𝑗𝑗 ⋅ ℐ𝓂𝓂{𝑋𝑋(𝑗𝑗𝜔𝜔)}
Even-Odd Decomposition
34
Example For 𝑎𝑎 > 0, let
𝑥𝑥 𝑡𝑡 = �𝑒𝑒−𝑎𝑎𝑡𝑡, 𝑡𝑡 > 0−𝑒𝑒𝑎𝑎𝑡𝑡 𝑡𝑡 < 0
• Let 𝑦𝑦 𝑡𝑡 = 𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢(𝑡𝑡), with 𝑌𝑌 𝑗𝑗𝜔𝜔 =
1𝑎𝑎 + 𝑗𝑗𝜔𝜔
• Since 𝑥𝑥 𝑡𝑡 = 𝑦𝑦 𝑡𝑡 − 𝑦𝑦(−𝑡𝑡)
𝑋𝑋 𝑗𝑗𝜔𝜔 = 𝑌𝑌 𝑗𝑗𝜔𝜔 − 𝑌𝑌(−𝑗𝑗𝜔𝜔)
=1
𝑎𝑎 + 𝑗𝑗𝜔𝜔−
1𝑎𝑎 − 𝑗𝑗𝜔𝜔
=−2𝑗𝑗𝜔𝜔𝑎𝑎2 + 𝜔𝜔2
• 𝑥𝑥 𝑡𝑡 real and odd ⟹ 𝑋𝑋 𝑗𝑗𝜔𝜔 purely imaginary and odd
35
Time and Frequency Scaling
𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔
𝑥𝑥 𝑎𝑎𝑡𝑡 ℱ 1
𝑎𝑎 𝑋𝑋𝑗𝑗𝜔𝜔𝑎𝑎 ,𝑎𝑎 ≠ 0
• Proof: change variables by 𝜏𝜏 = 𝑎𝑎𝑡𝑡 ▫ For 𝑎𝑎 > 0,
� 𝑥𝑥 𝑎𝑎𝑡𝑡 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 = � 𝑥𝑥 𝜏𝜏 𝑒𝑒−𝑗𝑗𝑗𝑗𝑎𝑎𝑗𝑗𝑑𝑑(
𝜏𝜏𝑎𝑎
) =1𝑎𝑎𝑋𝑋(𝑗𝑗𝜔𝜔𝑎𝑎
) +∞
−∞
+∞
−∞
▫ For 𝑎𝑎 < 0,
� 𝑥𝑥 𝑎𝑎𝑡𝑡 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 = � 𝑥𝑥 𝜏𝜏 𝑒𝑒−𝑗𝑗𝑗𝑗𝑎𝑎𝑗𝑗𝑑𝑑
𝜏𝜏𝑎𝑎
= −1𝑎𝑎𝑋𝑋(𝑗𝑗𝜔𝜔𝑎𝑎
) −∞
∞
+∞
−∞
36
Time and Frequency Scaling
𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 𝑥𝑥 𝑎𝑎𝑡𝑡 ℱ 1
𝑎𝑎 𝑋𝑋𝑗𝑗𝜔𝜔𝑎𝑎 ,𝑎𝑎 ≠ 0
compression in time ⟺ stretching in frequency stretching in time ⟺ compression in frequency
• Example: faster playback an audio clip ⟹ higher pitch
𝑥𝑥 𝑡𝑡 = 𝑒𝑒− 𝑎𝑎𝑡𝑡 2 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 =𝜋𝜋𝑎𝑎𝑒𝑒−
14𝑗𝑗𝑎𝑎
2
37
Exercise • Problem: If we have the Fourier transform pair
𝑥𝑥 𝑡𝑡 ↔ 𝑋𝑋 𝑗𝑗𝜔𝜔 ,
determine the Fourier transform for the signal 𝑥𝑥(𝑎𝑎𝑡𝑡 + 𝑏𝑏).
• Answer:
ℱ 𝑥𝑥 𝑎𝑎𝑡𝑡 + 𝑏𝑏 =1
|𝑎𝑎|𝑋𝑋(𝑗𝑗𝜔𝜔𝑎𝑎 )𝑒𝑒𝑗𝑗
𝑗𝑗𝜔𝜔𝑎𝑎
38
𝑥𝑥′ 𝑡𝑡 ℱ
𝑗𝑗𝜔𝜔𝑋𝑋 𝑗𝑗𝜔𝜔 , 𝑥𝑥 𝑘𝑘 𝑡𝑡 ℱ
𝑗𝑗𝜔𝜔 𝑘𝑘𝑋𝑋 𝑗𝑗𝜔𝜔
• Proof: differentiate both sides of FT synthesis equation
𝑥𝑥 𝑡𝑡 =12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔 ⟹ ∞
−∞𝑥𝑥′ 𝑡𝑡 =
12𝜋𝜋
� 𝑗𝑗𝜔𝜔𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞
• Example: differentiator 𝑦𝑦 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 , with frequency response
𝐻𝐻 𝑗𝑗𝜔𝜔 = ℱ 𝛿𝛿′ 𝑡𝑡 = � 𝛿𝛿′ 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡+∞
−∞
= 𝛿𝛿(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡�−∞
+∞+ 𝑗𝑗𝜔𝜔� 𝛿𝛿(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡
+∞
−∞= 𝑗𝑗𝜔𝜔
▫ 𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 𝐻𝐻(𝑗𝑗𝜔𝜔) ▫ amplifies high frequencies ▫ suppresses low frequencies ▫ DC completely eliminated, cannot be completely recovered from 𝑥𝑥′ 𝑡𝑡
Differentiation
39
𝑦𝑦 𝑡𝑡 = � 𝑥𝑥 𝜏𝜏 𝑑𝑑𝜏𝜏𝑡𝑡
−∞
ℱ 𝑌𝑌 𝑗𝑗𝜔𝜔 =
1𝑗𝑗𝜔𝜔
𝑋𝑋 𝑗𝑗𝜔𝜔 + 𝜋𝜋𝑋𝑋 0 𝛿𝛿(𝜔𝜔)
• Since 𝑥𝑥 𝑡𝑡 = 𝑦𝑦′ 𝑡𝑡 , by differentiation property
𝑋𝑋 𝑗𝑗𝜔𝜔 = 𝑗𝑗𝜔𝜔𝑌𝑌 𝑗𝑗𝜔𝜔 ⟹ 𝑌𝑌 𝑗𝑗𝜔𝜔 =1𝑗𝑗𝜔𝜔
𝑋𝑋 𝑗𝑗𝜔𝜔 ,∀𝜔𝜔 ≠ 0
• Intuitively, 𝑦𝑦(𝑡𝑡) has a DC component
𝑦𝑦� = lim𝑇𝑇→∞
12𝑇𝑇
� 𝑦𝑦 𝑡𝑡 𝑑𝑑𝑡𝑡𝑇𝑇
−𝑇𝑇= lim
𝑇𝑇→∞
12𝑇𝑇
� � 𝑥𝑥 𝜏𝜏 𝑢𝑢 𝑡𝑡 − 𝜏𝜏 𝑑𝑑𝜏𝜏∞
−∞𝑑𝑑𝑡𝑡
𝑇𝑇
−𝑇𝑇
= � 𝑥𝑥 𝜏𝜏 lim𝑇𝑇→∞
12𝑇𝑇
� 𝑢𝑢(𝑡𝑡 − 𝜏𝜏)𝑑𝑑𝑡𝑡𝑇𝑇
−𝑇𝑇𝑑𝑑𝜏𝜏
∞
−∞=
12� 𝑥𝑥 𝜏𝜏 𝑑𝑑𝜏𝜏∞
−∞=
12𝑋𝑋(0)
• Therefore, at 𝜔𝜔 = 0, 𝑌𝑌 𝑗𝑗𝜔𝜔 has a component 2𝜋𝜋𝑦𝑦�𝛿𝛿 𝜔𝜔 = 𝜋𝜋𝑋𝑋 0 𝛿𝛿(𝜔𝜔)
Integration
40
• Sign function:
sgn 𝑡𝑡 = � 1, 𝑡𝑡 > 0−1, 𝑡𝑡 < 0
ℱ
2𝑗𝑗𝜔𝜔
• Constant function:
1 ℱ
2𝜋𝜋𝛿𝛿(𝜔𝜔) • Unit step function:
𝑢𝑢 𝑡𝑡 =sgn 𝑡𝑡 + 1
2 ℱ
𝑈𝑈 𝑗𝑗𝜔𝜔 =1𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝛿𝛿 𝜔𝜔
• Integrator:
𝑦𝑦 𝑡𝑡 = � 𝑥𝑥 𝜏𝜏 𝑑𝑑𝜏𝜏𝑡𝑡
−∞= 𝑥𝑥 𝑡𝑡 ∗ 𝑢𝑢 𝑡𝑡
ℱ 𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑈𝑈 𝑗𝑗𝜔𝜔 =
1𝑗𝑗𝜔𝜔 𝑋𝑋 𝑗𝑗𝜔𝜔 + 𝜋𝜋𝑋𝑋 0 𝛿𝛿(𝜔𝜔)
Integration
41
• Sign function:
𝑥𝑥(𝑡𝑡) = �1 −2|𝑡𝑡|𝑇𝑇
, 𝑡𝑡 ≤𝑇𝑇2
0, otherwise
𝑋𝑋2 𝑗𝑗𝜔𝜔 =2𝑇𝑇
𝑒𝑒𝑗𝑗𝑗𝑗𝑇𝑇2 − 2 + 𝑒𝑒𝑗𝑗
𝑗𝑗𝑇𝑇2 = −
8𝑇𝑇
sin2𝜔𝜔𝑇𝑇4
𝑋𝑋1 𝑗𝑗𝜔𝜔 =𝑋𝑋2 𝑗𝑗𝜔𝜔𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝑋𝑋2 0 𝛿𝛿(𝜔𝜔) = −8𝑗𝑗𝜔𝜔𝑇𝑇
sin2𝜔𝜔𝑇𝑇4
𝑋𝑋 𝑗𝑗𝜔𝜔 =𝑋𝑋1 𝑗𝑗𝜔𝜔𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝑋𝑋1 0 𝛿𝛿(𝜔𝜔) =8
𝜔𝜔2𝑇𝑇sin2
𝜔𝜔𝑇𝑇4
Example: Triangular Pulse
42
Example: 𝐬𝐬𝐬𝐬𝐬𝐬 𝒕𝒕 Function • In terms of exponential function in the limit (𝑎𝑎 > 0)
𝑥𝑥 𝑡𝑡 = �𝑒𝑒−𝑎𝑎𝑡𝑡, 𝑡𝑡 > 0−𝑒𝑒𝑎𝑎𝑡𝑡 𝑡𝑡 < 0
sgn 𝑡𝑡 = lim𝑎𝑎→0
𝑥𝑥 (𝑡𝑡)
sgn 𝑡𝑡 ℱ
lim𝒂𝒂→0
𝑋𝑋 (𝑗𝑗𝜔𝜔)=2𝑗𝑗𝜔𝜔
• In terms of unit step functions
sgn 𝑡𝑡 = 𝑢𝑢 𝑡𝑡 − 𝑢𝑢(−𝑡𝑡)
sgn 𝑡𝑡 ℱ
[𝜋𝜋𝛿𝛿(𝜔𝜔) +1𝑗𝑗𝜔𝜔
] − [𝜋𝜋𝛿𝛿(−𝜔𝜔) +1
−𝑗𝑗𝜔𝜔] =
2𝑗𝑗𝜔𝜔
44
Example: 𝐬𝐬𝐬𝐬𝐬𝐬 𝒕𝒕 Function • Exploiting integration property
sgn 𝑡𝑡 = 2𝑢𝑢 𝑡𝑡 − 1 ≜ 𝑥𝑥 𝑡𝑡
sgn′ 𝑡𝑡 = 2𝛿𝛿(𝑡𝑡) ≜ 𝑥𝑥1 𝑡𝑡
𝑥𝑥1 𝑡𝑡 = 2𝛿𝛿 𝑡𝑡 ℱ
𝑋𝑋1 𝑗𝑗𝜔𝜔 = 2
sgn 𝑡𝑡 = 𝑥𝑥(𝑡𝑡) = 𝑥𝑥 −∞ + � 𝑥𝑥1(𝑡𝑡)𝑑𝑑𝑡𝑡𝑡𝑡
−∞
⟹ℱ sgn 𝑡𝑡 = 𝑋𝑋 𝑗𝑗𝜔𝜔 = 2𝜋𝜋𝑥𝑥 −∞ 𝛿𝛿 𝜔𝜔 +𝑋𝑋1(𝑗𝑗𝜔𝜔)𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝑋𝑋1(0)𝛿𝛿(𝜔𝜔)
= 2𝜋𝜋 ⋅ −1 ⋅ 𝛿𝛿 𝜔𝜔 +2𝑗𝑗𝜔𝜔
+ 𝜋𝜋 ⋅ 2𝛿𝛿(𝜔𝜔) =2𝑗𝑗𝜔𝜔
45
Duality • Both time and frequency functions are continuous and aperiodic
in general, identical form except for ▫ different signs in exponent of complex exponential ▫ constant factor 1/2𝜋𝜋
𝑥𝑥 𝑡𝑡 =1
2𝜋𝜋� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡∞
−∞𝑑𝑑𝜔𝜔
ℱ 𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡
∞
−∞𝑑𝑑𝑡𝑡
• Suppose two functions are related by
𝑓𝑓 𝑟𝑟 = � 𝑔𝑔(𝜏𝜏)𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗∞
−∞𝑑𝑑𝜏𝜏
▫ Let 𝜏𝜏 = 𝑡𝑡, and 𝑟𝑟 = 𝜔𝜔, ⟹ 𝑔𝑔 𝑡𝑡 ℱ
𝑓𝑓 𝜔𝜔
▫ Let 𝜏𝜏 = −𝜔𝜔, and 𝑟𝑟 = 𝑡𝑡,⟹ 𝑓𝑓 𝑡𝑡 ℱ
2𝜋𝜋𝑔𝑔 −𝜔𝜔
• Duality: 𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 ⟺ 𝑋𝑋(𝑡𝑡) ℱ
2𝜋𝜋𝑥𝑥(−𝑗𝑗𝜔𝜔)
46
Duality Example: 𝑥𝑥 𝑡𝑡 = 1
𝜋𝜋𝑡𝑡
• Known
sgn 𝑡𝑡 ℱ 2
𝑗𝑗𝜔𝜔
• By duality ▫ switch LHS and RHS, switch 𝜔𝜔 and 𝑡𝑡 ▫ substitute 𝜔𝜔 → −𝜔𝜔 or 𝑡𝑡 → −𝑡𝑡 (but not both) ▫ multiply RHS by 2𝜋𝜋
−2𝑗𝑗𝑡𝑡
ℱ 2𝜋𝜋 ⋅ sgn 𝜔𝜔
• By linearity 1𝜋𝜋𝑡𝑡
ℱ − 𝑗𝑗 ⋅ sgn 𝜔𝜔
48
𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 ⟺ 𝑋𝑋(𝑡𝑡) ℱ
2𝜋𝜋𝑥𝑥(−𝑗𝑗𝜔𝜔)
Duality Example: 𝑥𝑥(𝑡𝑡) = 1
1+𝑡𝑡2
• Known
𝑒𝑒−|𝑡𝑡| ℱ 21 + 𝜔𝜔2
• By duality ▫ switch LHS and RHS, switch 𝜔𝜔 and 𝑡𝑡 ▫ substitute 𝜔𝜔 → −𝜔𝜔 or 𝑡𝑡 → −𝑡𝑡 (but not both) ▫ multiply RHS by 2𝜋𝜋
21 + 𝑡𝑡2
ℱ
2𝜋𝜋 ⋅ 𝑒𝑒−|𝑗𝑗|
• By linearity 1
1 + 𝑡𝑡2 ℱ
𝜋𝜋 ⋅ 𝑒𝑒−|𝑗𝑗|
49
𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋 𝑗𝑗𝜔𝜔 ⟺ 𝑋𝑋(𝑡𝑡) ℱ
2𝜋𝜋𝑥𝑥(−𝑗𝑗𝜔𝜔)
Duality • Differentiation in frequency
−𝑗𝑗𝑡𝑡𝑥𝑥 𝑡𝑡 ℱ 𝑑𝑑𝑋𝑋 𝑗𝑗𝜔𝜔
𝑑𝑑𝜔𝜔, 𝑡𝑡𝑥𝑥 𝑡𝑡
ℱ 𝑗𝑗𝑑𝑑𝑋𝑋(𝑗𝑗𝜔𝜔)𝑑𝑑𝜔𝜔
• Proof:
𝑋𝑋 𝑗𝑗𝜔𝜔 = � 𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡∞
−∞𝑑𝑑𝑡𝑡 ⟹
𝑑𝑑𝑋𝑋 𝑗𝑗𝜔𝜔𝑑𝑑𝜔𝜔
= � (−𝑗𝑗𝑡𝑡)𝑥𝑥(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡∞
−∞𝑑𝑑𝑡𝑡
• Example: Unit ramp function 𝑢𝑢−2 𝑡𝑡 = ∫ 𝑢𝑢 𝜏𝜏 𝑑𝑑𝜏𝜏𝑡𝑡−∞ = 𝑡𝑡𝑢𝑢(𝑡𝑡)
ℱ 𝑢𝑢−2 𝑡𝑡 = 𝑗𝑗ℱ −𝑗𝑗𝑡𝑡𝑢𝑢(𝑡𝑡) = 𝑗𝑗𝑑𝑑𝑈𝑈(𝑗𝑗𝜔𝜔)𝑑𝑑𝜔𝜔
= −1𝜔𝜔2 + 𝑗𝑗𝜋𝜋𝛿𝛿′(𝜔𝜔)
• Integration in frequency
−1𝑗𝑗𝑡𝑡𝑥𝑥 𝑡𝑡 + 𝜋𝜋𝑥𝑥 0 𝛿𝛿 𝑡𝑡
ℱ � 𝑋𝑋 𝜂𝜂 𝑑𝑑𝜂𝜂
𝑗𝑗
−∞
50
Example
• Problem: 𝑥𝑥 𝑡𝑡 = 𝑡𝑡𝑒𝑒−2𝑡𝑡𝑢𝑢 𝑡𝑡 ℱ
?
• Solution:
𝑒𝑒−2𝑡𝑡𝑢𝑢 𝑡𝑡 ℱ 1
2 + 𝑗𝑗𝜔𝜔
𝑡𝑡𝑒𝑒−2𝑡𝑡𝑢𝑢 𝑡𝑡 ℱ
𝑗𝑗𝑑𝑑𝑑𝑑𝜔𝜔
12 + 𝑗𝑗𝜔𝜔 =
1(2 + 𝑗𝑗𝜔𝜔)2
• Exercise: 𝑥𝑥 𝑡𝑡 = 𝑡𝑡𝑒𝑒−2𝑡𝑡𝑢𝑢 𝑡𝑡 − 1 ↔?
51
Exercise • Determine 𝑥𝑥(𝑡𝑡) according to 𝑋𝑋 𝑗𝑗𝜔𝜔
• Hints: exploit integration property in frequency domain
𝑥𝑥1 𝑡𝑡 ℱ
𝑋𝑋′ 𝑗𝑗𝜔𝜔 ⟹ 𝑥𝑥 𝑡𝑡 = 𝑥𝑥1 𝑡𝑡−𝑗𝑗𝑡𝑡
+ 𝜋𝜋𝑥𝑥1 0 𝛿𝛿 𝑡𝑡
where 𝑥𝑥1 0 = ∫𝑋𝑋′(𝑗𝑗𝜔𝜔)𝑑𝑑𝜔𝜔 = 0
52
−𝜔𝜔1 𝜔𝜔1
𝑋𝑋(𝑗𝑗𝜔𝜔)
1
𝑋𝑋′(𝑗𝑗𝜔𝜔)
𝜔𝜔1 −𝜔𝜔1
1/𝜔𝜔1
-1/𝜔𝜔1
• For a Fourier transform pair 𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋(𝑗𝑗𝜔𝜔)
� 𝑥𝑥 𝑡𝑡 2∞
−∞𝑑𝑑𝑡𝑡 =
12𝜋𝜋
� 𝑋𝑋(𝑗𝑗𝜔𝜔) 2∞
−∞𝑑𝑑𝜔𝜔 = � 𝑋𝑋 𝑗𝑗𝜔𝜔 2
∞
−∞
𝑑𝑑𝜔𝜔2𝜋𝜋
• Note: 𝜔𝜔 is angular frequency and 𝑓𝑓 = 𝜔𝜔/2𝜋𝜋 is frequency
• Interpretation: Energy conservation ▫ 𝑥𝑥 𝑡𝑡 2: power, or energy per unit time (in second) ▫ 𝑋𝑋(𝑗𝑗𝜔𝜔) 2: energy per unit frequency (in Hertz), called energy-
density spectrum
• lim𝑇𝑇→∞
1𝑇𝑇 ∫ |𝑥𝑥(𝑡𝑡)|2𝑑𝑑𝑡𝑡 = 1
2𝜋𝜋𝑇𝑇 ∫ lim𝑇𝑇→∞
|𝑋𝑋(𝑗𝑗𝑗𝑗)|2
𝑇𝑇∞−∞ 𝑑𝑑𝜔𝜔
▫ lim𝑇𝑇→∞
|𝑋𝑋(𝑗𝑗𝑗𝑗)|2
𝑇𝑇 : called power-density spectrum
Parseval’s Relation
53
• For a Fourier transform pair 𝑥𝑥 𝑡𝑡 ℱ
𝑋𝑋(𝑗𝑗𝜔𝜔)
� 𝑥𝑥 𝑡𝑡 2∞
−∞𝑑𝑑𝑡𝑡 =
12𝜋𝜋
� 𝑋𝑋(𝑗𝑗𝜔𝜔) 2∞
−∞𝑑𝑑𝜔𝜔 = � 𝑋𝑋 𝑗𝑗𝜔𝜔 2
∞
−∞
𝑑𝑑𝜔𝜔2𝜋𝜋
• Proof:
� 𝑥𝑥 𝑡𝑡 2∞
−∞𝑑𝑑𝑡𝑡 = � 𝑥𝑥 𝑡𝑡 𝑥𝑥∗ 𝑡𝑡
∞
−∞𝑑𝑑𝑡𝑡 = � 𝑥𝑥 𝑡𝑡
12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔∞
−∞𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∗∞
−∞𝑑𝑑𝑡𝑡
= � 𝑥𝑥 𝑡𝑡12𝜋𝜋
� 𝑋𝑋∗ 𝑗𝑗𝜔𝜔∞
−∞𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
∞
−∞𝑑𝑑𝑡𝑡
=12𝜋𝜋
� 𝑋𝑋∗ 𝑗𝑗𝜔𝜔 � 𝑥𝑥 𝑡𝑡∞
−∞𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡
∞
−∞𝑑𝑑𝜔𝜔
=12𝜋𝜋
� 𝑋𝑋∗ 𝑗𝑗𝜔𝜔 𝑋𝑋(𝑗𝑗𝜔𝜔)∞
−∞𝑑𝑑𝜔𝜔 =
12𝜋𝜋
� 𝑋𝑋(𝑗𝑗𝜔𝜔) 2∞
−∞𝑑𝑑𝜔𝜔
Parseval’s Relation
54
• Example: determine the following time domain expressions:
𝐸𝐸 = � 𝑥𝑥 𝑡𝑡 |2𝑑𝑑𝑡𝑡, and 𝐷𝐷 = 𝑥𝑥′ 𝑡𝑡 𝑡𝑡=0
∞
−∞
• Solution:
𝐸𝐸 = � |𝑥𝑥 𝑡𝑡 |2𝑑𝑑𝑡𝑡∞
−∞
=12𝜋𝜋
� 𝑋𝑋(𝑗𝑗𝜔𝜔) 2∞
−∞𝑑𝑑𝜔𝜔 =
12𝜋𝜋
⋅5𝜋𝜋4
=58
𝑔𝑔 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 ℱ
𝐺𝐺 𝑗𝑗𝜔𝜔 = 𝑗𝑗𝜔𝜔𝑋𝑋(𝑗𝑗𝜔𝜔)
⟹ 𝐷𝐷 = 𝑔𝑔 0 =12𝜋𝜋
� 𝐺𝐺 𝑗𝑗𝜔𝜔∞
−∞𝑑𝑑𝜔𝜔 =
12𝜋𝜋
� 𝑗𝑗𝜔𝜔𝑋𝑋 𝑗𝑗𝜔𝜔 ∞
−∞𝑑𝑑𝜔𝜔 = 0
Parseval’s Relation
55
𝑋𝑋(𝑗𝑗𝜔𝜔) 𝜋𝜋
𝜋𝜋/2
-1 -0.5 1 0.5
• Example: sin 𝑊𝑊𝑡𝑡𝜋𝜋𝑡𝑡
ℱ
𝑢𝑢 𝜔𝜔 + 𝑊𝑊 − 𝑢𝑢(𝜔𝜔 −𝑊𝑊)
• By Parseval’s relation
�sin2 𝑊𝑊𝑡𝑡𝜋𝜋2𝑡𝑡2
𝑑𝑑𝑡𝑡 =12𝜋𝜋
∞
−∞� 𝑢𝑢 𝜔𝜔 + 𝑊𝑊 − 𝑢𝑢(𝜔𝜔 −𝑊𝑊) 2∞
−∞𝑑𝑑𝜔𝜔
=12𝜋𝜋
� 1𝑊𝑊
−𝑊𝑊𝑑𝑑𝜔𝜔
=𝑊𝑊𝜋𝜋
Parseval’s Relation
56
Example • Use Fourier transform of typical signals and Fourier
transform properties to determine the Fourier transform of the following signal
57
-1 -2 1 2
1
2
𝑥𝑥(𝑡𝑡)
Example
• Solution 1: 𝑥𝑥 𝑡𝑡 = 2𝑔𝑔2 𝑡𝑡 + 𝑢𝑢 −𝑡𝑡 − 2 + 𝑢𝑢(𝑡𝑡 − 2)
▫ 𝑔𝑔𝜏𝜏(𝑡𝑡) is the rectangular pulse with width of 𝜏𝜏 and unit magnitude
58
-1 -2 1 2
1
2
𝑥𝑥(𝑡𝑡)
1 -1
2
+
-2
1 +
2
1
Example
• Solution 2: ▫ Assume
𝑥𝑥1 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 ℱ
𝑋𝑋1(𝑗𝑗𝜔𝜔)
▫ Then
𝑋𝑋 𝑗𝑗𝜔𝜔 = 2𝜋𝜋𝑥𝑥 −∞ 𝛿𝛿 𝜔𝜔 +𝑋𝑋1(𝑗𝑗𝜔𝜔)𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝑋𝑋1 0 𝛿𝛿 𝜔𝜔
59
-1 -2 1 2
1
2
𝑥𝑥(𝑡𝑡)
-1
1
2
-2
1 2
𝑥𝑥′(𝑡𝑡)
-1 -2
Exercise • Determine the inverse Fourier transform
▫ Plot 1:
▫ Plot 2:
60
0ω− 0ω
A
|)(| ωjX )( ωjX∠
0ω− 0ω w
A
|)(| ωjX )( ωjX∠
0ω0ω−
2/π
2/π−
Note: different
phase spectrum
Exercise • Determine the Fourier transform of the following signals
▫ 𝑥𝑥(𝑡𝑡) = 𝑒𝑒−2𝑡𝑡𝑢𝑢(𝑡𝑡)
▫ 𝑥𝑥 𝑡𝑡 = 𝑒𝑒−2 𝑡𝑡−1 𝑢𝑢 𝑡𝑡
▫ 𝑥𝑥(𝑡𝑡) = 𝑒𝑒−2𝑡𝑡𝑢𝑢(𝑡𝑡 − 1)
61
Convolution Property
𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 ∗ ℎ 𝑡𝑡 ℱ
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 𝐻𝐻(𝑗𝑗𝜔𝜔)
convolution in time ⟺ multiplication in frequency
• Proof:
𝑌𝑌 𝑗𝑗𝜔𝜔 = � 𝑦𝑦 𝑡𝑡 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 = � 𝑥𝑥 𝑡𝑡 ∗ ℎ(𝑡𝑡)𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡+∞
−∞
+∞
−∞
= � � 𝑥𝑥 𝜏𝜏 ℎ(𝑡𝑡 − 𝜏𝜏)+∞
−∞𝑑𝑑𝜏𝜏 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡
+∞
−∞
= � 𝑥𝑥 𝜏𝜏 � ℎ(𝑡𝑡 − 𝜏𝜏)+∞
−∞𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 𝑑𝑑𝜏𝜏
+∞
−∞
= � 𝑥𝑥 𝜏𝜏 𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗𝐻𝐻 𝑗𝑗𝜔𝜔 𝑑𝑑𝜏𝜏+∞
−∞= 𝐻𝐻 𝑗𝑗𝜔𝜔 � 𝑥𝑥 𝜏𝜏 𝑒𝑒−𝑗𝑗𝑗𝑗𝑗𝑗𝑑𝑑𝜏𝜏
+∞
−∞= 𝐻𝐻(𝑗𝑗𝜔𝜔)𝑋𝑋(𝑗𝑗𝜔𝜔)
62
Convolution Property • For an LTI system with ▫ impulse response ℎ(𝑡𝑡) ▫ frequency response 𝐻𝐻 𝑗𝑗𝜔𝜔 = ∫ ℎ 𝑡𝑡∞
−∞ 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝑡𝑡 = ℱ{ℎ 𝑡𝑡 }
▫ 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡 is eigenfunction associated with eigenvalue 𝐻𝐻 𝑗𝑗𝜔𝜔
𝑥𝑥 𝑡𝑡 = 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡 → 𝑦𝑦 𝑡𝑡 = � ℎ 𝜏𝜏 𝑒𝑒𝑗𝑗𝑗𝑗(𝑡𝑡−𝑗𝑗)𝑑𝑑𝜏𝜏∞
−∞= 𝐻𝐻 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡
• Input 𝑥𝑥 𝑡𝑡 as a linear combination of complex exponentials
𝑥𝑥 𝑡𝑡 =12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞= lim
𝑗𝑗0→0
12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
⇒ 𝑦𝑦 𝑡𝑡 = lim𝑗𝑗0→0
12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝑘𝑘𝜔𝜔0 𝐻𝐻 𝑗𝑗𝑘𝑘𝜔𝜔0 𝑒𝑒𝑗𝑗𝑘𝑘𝑗𝑗0𝑡𝑡𝜔𝜔0
∞
𝑘𝑘=−∞
=12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜔𝜔 𝐻𝐻 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞=
12𝜋𝜋
� 𝑌𝑌 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔∞
−∞
63
• Rectangular pulse:
𝑥𝑥1 𝑡𝑡 = 2/𝑇𝑇 𝑢𝑢 𝑡𝑡 +𝑇𝑇4
− 𝑢𝑢(𝑡𝑡 −𝑇𝑇4
)
𝑋𝑋1 𝑗𝑗𝜔𝜔 = 2/𝑇𝑇 ⋅2 sin(𝜔𝜔𝑇𝑇/4)
𝜔𝜔
• Triangular pulse:
𝑥𝑥(𝑡𝑡) = 1 −2|𝑡𝑡|𝑇𝑇
𝑢𝑢 𝑡𝑡 +𝑇𝑇2
− 𝑢𝑢(𝑡𝑡 −𝑇𝑇2
)
𝑋𝑋1 𝑗𝑗𝜔𝜔 = 𝑋𝑋12 𝑗𝑗𝜔𝜔 =8 sin2(𝜔𝜔𝑇𝑇/4)
𝜔𝜔2𝑇𝑇
Example
64
Frequency Response of LTI Systems • Fully characterized by impulse response ℎ(𝑡𝑡)
𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 ∗ ℎ 𝑡𝑡
• Also fully characterized by frequency response 𝐻𝐻 𝑗𝑗𝜔𝜔 =ℱ{ℎ 𝑡𝑡 }, if 𝐻𝐻 𝑗𝑗𝜔𝜔 is well defined ▫ BIBO stable system: ∫ ℎ 𝑡𝑡 𝑑𝑑𝑡𝑡 < ∞+∞
−∞ ▫ other systems: e.g., identity ℎ 𝑡𝑡 = 𝛿𝛿(𝑡𝑡), differentiator ℎ 𝑡𝑡 = 𝛿𝛿′(𝑡𝑡)
• Convolution property implies ▫ instead of computing 𝑥𝑥 𝑡𝑡 ∗ ℎ 𝑡𝑡 in time domain, we can analyze
a system in frequency domain 𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 ∗ ℎ(𝑡𝑡)
⇓
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 ⋅ 𝐻𝐻 𝑗𝑗𝜔𝜔 , 𝐻𝐻 𝑗𝑗𝜔𝜔 =𝑌𝑌 𝑗𝑗𝜔𝜔𝑋𝑋 𝑗𝑗𝜔𝜔
= 𝐻𝐻 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑗 𝑗𝑗𝑗𝑗
65
• Example: Differentiation property
𝑦𝑦 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 ∗ 𝛿𝛿′ 𝑡𝑡
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 ⋅ ℱ 𝛿𝛿′ 𝑡𝑡 = 𝑗𝑗𝜔𝜔 ⋅ 𝑋𝑋(𝑗𝑗𝜔𝜔)
• Example. Integration property
𝑦𝑦 𝑡𝑡 = � 𝑥𝑥 𝜏𝜏 𝑑𝑑𝜏𝜏𝑡𝑡
−∞= 𝑥𝑥 𝑡𝑡 ∗ 𝑢𝑢 𝑡𝑡
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋 𝑗𝑗𝜔𝜔 ⋅ 𝑈𝑈(𝑗𝑗𝜔𝜔) = 𝑋𝑋 𝑗𝑗𝜔𝜔1𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝛿𝛿 𝜔𝜔
=1𝑗𝑗𝜔𝜔
𝑋𝑋 𝑗𝑗𝜔𝜔 + 𝜋𝜋𝑋𝑋 0 𝛿𝛿 𝜔𝜔
Examples
67
• Unit ramp function: 𝑢𝑢−2 𝑡𝑡 = 𝑢𝑢 𝑡𝑡 ∗ 𝑢𝑢(𝑡𝑡) = 𝑡𝑡𝑢𝑢(𝑡𝑡)
• Convolution property suggests
ℱ 𝑢𝑢−2 𝑡𝑡 = 𝑈𝑈2 𝑗𝑗𝜔𝜔 =1𝑗𝑗𝜔𝜔
+ 𝜋𝜋𝛿𝛿 𝜔𝜔2
= −1𝜔𝜔2 +
2𝜋𝜋𝑗𝑗𝜔𝜔
𝛿𝛿 𝜔𝜔 + 𝜋𝜋2𝛿𝛿 𝜔𝜔 𝛿𝛿(𝜔𝜔)
▫ But 𝛿𝛿(𝑗𝑗)𝑗𝑗𝑗𝑗
and 𝛿𝛿 𝜔𝜔 𝛿𝛿(𝜔𝜔) not well-defined!
▫ Convolution property not applicable here ▫ Rule of thumb: applicable when formula is well-defined
• Known from the differentiation in frequency property
ℱ 𝑢𝑢−2 𝑡𝑡 = 𝑗𝑗ℱ −𝑗𝑗𝑡𝑡𝑢𝑢(𝑡𝑡) = 𝑗𝑗𝑑𝑑𝑈𝑈(𝑗𝑗𝜔𝜔)𝑑𝑑𝜔𝜔
= −1𝜔𝜔2 + 𝑗𝑗𝜋𝜋𝛿𝛿′(𝜔𝜔)
Example
68
Example • Determine the Response of an LTI system with impulse response ℎ 𝑡𝑡 = 𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢(𝑡𝑡), to the input 𝑥𝑥(𝑡𝑡) = 𝑒𝑒−𝜔𝜔𝑡𝑡𝑢𝑢(𝑡𝑡), where 𝑎𝑎, 𝑏𝑏 > 0
• Method 1: convolution in time domain 𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 ∗ ℎ 𝑡𝑡
• Method 2: solving the differential equation with initial rest condition 𝑦𝑦′ 𝑡𝑡 + 𝑎𝑎𝑦𝑦 𝑡𝑡 = 𝑒𝑒−𝜔𝜔𝑡𝑡𝑢𝑢(𝑡𝑡)
• Method 3: Fourier transform
𝐻𝐻 𝑗𝑗𝜔𝜔 =1
𝑎𝑎 + 𝑗𝑗𝜔𝜔,𝑋𝑋 𝑗𝑗𝜔𝜔 =
1𝑏𝑏 + 𝑗𝑗𝜔𝜔
⟹ 𝑌𝑌 𝑗𝑗𝜔𝜔 =1
(𝑎𝑎 + 𝑗𝑗𝜔𝜔)(𝑏𝑏 + 𝑗𝑗𝜔𝜔)
▫ If 𝑎𝑎 ≠ 𝑏𝑏,𝑌𝑌 𝑗𝑗𝜔𝜔 = 1𝜔𝜔−𝑎𝑎
1𝑎𝑎+𝑗𝑗𝑗𝑗
− 1𝜔𝜔+𝑗𝑗𝑗𝑗
⟹ 𝑦𝑦 𝑡𝑡 = 1𝜔𝜔−𝑎𝑎
𝑒𝑒−𝑎𝑎𝑡𝑡 − 𝑒𝑒−𝜔𝜔𝑡𝑡 𝑢𝑢(𝑡𝑡)
▫ If 𝑎𝑎 = 𝑏𝑏,𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑗𝑗 𝑑𝑑𝑑𝑑𝑗𝑗
1𝑎𝑎+𝑗𝑗𝑗𝑗
⟹ 𝑦𝑦 𝑡𝑡 = 𝑡𝑡 ⋅ ℱ−1{ 1𝑎𝑎+𝑗𝑗𝑗𝑗
} = 𝑡𝑡𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢(𝑡𝑡)
69
Example • Determine the Response of an LTI system with impulse response ℎ 𝑡𝑡 = 𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢(𝑡𝑡), to the input 𝑥𝑥 𝑡𝑡 = cos(𝜔𝜔0𝑡𝑡), where 𝑎𝑎 > 0
• Frequency response:
𝐻𝐻 𝑗𝑗𝜔𝜔 =1
𝑎𝑎 + 𝑗𝑗𝜔𝜔=
𝑎𝑎 − 𝑗𝑗𝜔𝜔𝑎𝑎2 + 𝜔𝜔2 =
1𝑎𝑎2 + 𝜔𝜔2
𝑒𝑒−𝑗𝑗⋅arc𝑗an(𝑗𝑗/𝑎𝑎)
• Method 1: using eigenfunction property
𝑥𝑥 𝑡𝑡 =12𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 +
12𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡
𝑦𝑦 𝑡𝑡 =12𝐻𝐻 𝑗𝑗𝜔𝜔0 𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 +
12𝐻𝐻 −𝑗𝑗𝜔𝜔0 𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡 = ℛℯ 𝐻𝐻 𝑗𝑗𝜔𝜔0 𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡
=𝑎𝑎 cos(𝜔𝜔0𝑡𝑡) + 𝜔𝜔0sin(𝜔𝜔0𝑡𝑡)
𝑎𝑎2 + 𝜔𝜔02= 1/ 𝑎𝑎2 + 𝜔𝜔02 cos 𝜔𝜔0𝑡𝑡 − arctan
𝜔𝜔𝑎𝑎
70
Example • Determine the Response of an LTI system with impulse response ℎ 𝑡𝑡 = 𝑒𝑒−𝑎𝑎𝑡𝑡𝑢𝑢(𝑡𝑡), to the input 𝑥𝑥 𝑡𝑡 = cos(𝜔𝜔0𝑡𝑡), where 𝑎𝑎 > 0
• Frequency response:
𝐻𝐻 𝑗𝑗𝜔𝜔 =1
𝑎𝑎 + 𝑗𝑗𝜔𝜔=
𝑎𝑎 − 𝑗𝑗𝜔𝜔𝑎𝑎2 + 𝜔𝜔2 =
1𝑎𝑎2 + 𝜔𝜔2
𝑒𝑒−𝑗𝑗⋅arc𝑗an(𝑗𝑗/𝑎𝑎)
• Method 2: using Fourier transform
𝑥𝑥 𝑡𝑡 =12𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 +
12𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡 ⟹ 𝑋𝑋 𝑗𝑗𝜔𝜔 = 𝜋𝜋𝛿𝛿 𝜔𝜔 − 𝜔𝜔0 + 𝜋𝜋𝛿𝛿(𝜔𝜔 + 𝜔𝜔0)
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋(𝑗𝑗𝜔𝜔)𝐻𝐻 𝑗𝑗𝜔𝜔 = 𝜋𝜋𝐻𝐻 𝑗𝑗𝜔𝜔0 𝛿𝛿 𝜔𝜔 − 𝜔𝜔0 + 𝜋𝜋𝐻𝐻 −𝑗𝑗𝜔𝜔0 𝛿𝛿(𝜔𝜔 + 𝜔𝜔0)
⟹ 𝑦𝑦 𝑡𝑡 =12𝐻𝐻 𝑗𝑗𝜔𝜔0 𝑒𝑒𝑗𝑗𝑗𝑗0𝑡𝑡 +
12𝐻𝐻 −𝑗𝑗𝜔𝜔0 𝑒𝑒−𝑗𝑗𝑗𝑗0𝑡𝑡
71
Example • Ideal lowpass filter with impulse response ℎ 𝑡𝑡 to input 𝑥𝑥 𝑡𝑡
ℎ 𝑡𝑡 =sin(𝜔𝜔𝑐𝑐𝑡𝑡)
𝜋𝜋𝑡𝑡, 𝑥𝑥 𝑡𝑡 =
sin(𝜔𝜔𝑖𝑖𝑡𝑡)𝜋𝜋𝑡𝑡
• Fourier transform:
𝑋𝑋 𝑗𝑗𝜔𝜔 = 𝑢𝑢 𝜔𝜔 + 𝜔𝜔𝑖𝑖 − 𝑢𝑢(𝜔𝜔 − 𝜔𝜔𝑖𝑖)
𝐻𝐻 𝑗𝑗𝜔𝜔 = 𝑢𝑢 𝜔𝜔 + 𝜔𝜔𝑐𝑐 − 𝑢𝑢(𝜔𝜔 − 𝜔𝜔𝑐𝑐)
• Use 𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑋𝑋(𝑗𝑗𝜔𝜔)𝐻𝐻 𝑗𝑗𝜔𝜔
𝑌𝑌 𝑗𝑗𝜔𝜔 = �𝑋𝑋 𝑗𝑗𝜔𝜔 , if 𝜔𝜔𝑖𝑖 ≤ 𝜔𝜔𝑐𝑐𝐻𝐻 𝑗𝑗𝜔𝜔 , if 𝜔𝜔𝑖𝑖 > 𝜔𝜔𝑐𝑐
⟹ 𝑦𝑦 𝑡𝑡 = �𝑥𝑥(𝑡𝑡), if 𝜔𝜔𝑖𝑖 ≤ 𝜔𝜔𝑐𝑐ℎ(𝑡𝑡), if 𝜔𝜔𝑖𝑖 > 𝜔𝜔𝑐𝑐
• Note: Convolution of two 𝑠𝑠𝑠𝑠𝑛𝑛𝑠𝑠() functions is another 𝑠𝑠𝑠𝑠𝑛𝑛𝑠𝑠() function
72
𝑦𝑦 = (𝑥𝑥 ∗ ℎ1) ∗ ℎ2 = 𝑥𝑥 ∗ (ℎ1 ∗ ℎ2) = (𝑥𝑥 ∗ ℎ2) ∗ ℎ1 ℎ(𝑡𝑡) = ℎ1(𝑡𝑡) ∗ ℎ2(𝑡𝑡) ℎ(𝑡𝑡) = ℎ2(𝑡𝑡) ∗ ℎ1(𝑡𝑡) Note: Order of processing usually not important for LTI systems
System Connections: Cascade
73
ℎ1(𝑡𝑡) 𝑥𝑥(𝑡𝑡) 𝑦𝑦(𝑡𝑡) ℎ2(𝑡𝑡) h(𝑡𝑡)
ℎ2(𝑡𝑡) 𝑥𝑥(𝑡𝑡) 𝑦𝑦(𝑡𝑡) ℎ1(𝑡𝑡) h(𝑡𝑡)
commutative
𝑌𝑌 = 𝑋𝑋 ⋅ 𝐻𝐻1 ⋅ 𝐻𝐻2= 𝑋𝑋 ⋅ 𝐻𝐻1 ⋅ 𝐻𝐻2 = 𝑋𝑋 ⋅ 𝐻𝐻2 ⋅ 𝐻𝐻1 𝐻𝐻(𝑗𝑗𝜔𝜔) = 𝐻𝐻1(𝑗𝑗𝜔𝜔)𝐻𝐻2(𝑗𝑗𝜔𝜔)
𝐻𝐻(𝑗𝑗𝜔𝜔) = 𝐻𝐻2(𝑗𝑗𝜔𝜔)𝐻𝐻1(𝑗𝑗𝜔𝜔) Note: Order of processing usually not important for LTI systems
System Connections: Cascade
74
𝐻𝐻1(𝑗𝑗𝜔𝜔) 𝑥𝑥(𝑡𝑡) 𝑦𝑦(𝑡𝑡) 𝐻𝐻2(𝑗𝑗𝜔𝜔) 𝐻𝐻(𝑗𝑗𝜔𝜔)
𝐻𝐻2(𝑗𝑗𝜔𝜔) 𝑥𝑥(𝑡𝑡) 𝑦𝑦(𝑡𝑡) 𝐻𝐻1(𝑗𝑗𝜔𝜔)
commutative
𝐻𝐻(𝑗𝑗𝜔𝜔)
System Connections: Parallel • Time domain
ℎ 𝑡𝑡 = ℎ1 𝑡𝑡 + ℎ2(𝑡𝑡)
• Frequency domain
𝐻𝐻 𝑗𝑗𝜔𝜔 = 𝐻𝐻1 𝑗𝑗𝜔𝜔 + 𝐻𝐻2(𝑗𝑗𝜔𝜔)
75
ℎ1(𝑡𝑡) 𝑦𝑦(𝑡𝑡)
ℎ2(𝑡𝑡) 𝑥𝑥(𝑡𝑡) +
ℎ 𝑡𝑡
𝐻𝐻1(𝑗𝑗𝜔𝜔) 𝑦𝑦(𝑡𝑡)
𝐻𝐻2(𝑗𝑗𝜔𝜔) 𝑥𝑥(𝑡𝑡) +
𝐻𝐻 𝑗𝑗𝜔𝜔
System Connections: Feedback • Time domain 𝑦𝑦 = ℎ1 ∗ 𝑥𝑥 − ℎ2 ∗ 𝑦𝑦 ℎ 𝑡𝑡 = ?
• Frequency domain
𝑌𝑌 = 𝐻𝐻1𝑋𝑋 − 𝐻𝐻1𝐻𝐻2𝑌𝑌
𝐻𝐻 =𝑌𝑌𝑋𝑋 =
𝐻𝐻11 + 𝐻𝐻1𝐻𝐻2
76
ℎ1(𝑡𝑡) 𝑦𝑦(𝑡𝑡)
ℎ2(𝑡𝑡)
𝑥𝑥(𝑡𝑡)
ℎ 𝑡𝑡
+ +
-
𝐻𝐻1(𝑗𝑗𝜔𝜔) 𝑦𝑦(𝑡𝑡)
𝐻𝐻2(𝑗𝑗𝜔𝜔)
𝑥𝑥(𝑡𝑡)
𝐻𝐻 𝑗𝑗𝜔𝜔
+ +
-
Filtering • changes relative amplitudes of frequency components, or eliminates
some frequency components entirely
• LPS:
• HPS:
• BPS:
77
𝐻𝐻(𝑗𝑗𝜔𝜔)
𝜔𝜔𝑐𝑐 −𝜔𝜔𝑐𝑐
1
𝜔𝜔
passband stopband cutoff frequency
𝐻𝐻(𝑗𝑗𝜔𝜔)
𝐻𝐻(𝑗𝑗𝜔𝜔)
𝐻𝐻(𝑗𝑗𝜔𝜔) = �1, 𝜔𝜔 ≤ 𝜔𝜔𝑐𝑐0, 𝜔𝜔 > 𝜔𝜔𝑐𝑐
𝐻𝐻(𝑗𝑗𝜔𝜔) = �1, 𝜔𝜔 ≥ 𝜔𝜔𝑐𝑐0, 𝜔𝜔 < 𝜔𝜔𝑐𝑐
𝐻𝐻(𝑗𝑗𝜔𝜔) = �1, 𝜔𝜔𝑐𝑐1 < 𝜔𝜔 < 𝜔𝜔𝑐𝑐20, otherwise
𝜔𝜔𝑐𝑐 −𝜔𝜔𝑐𝑐 𝜔𝜔
𝜔𝜔𝑐𝑐1 −𝜔𝜔𝑐𝑐1 𝜔𝜔 −𝜔𝜔𝑐𝑐2
lower cutoff frequency
𝜔𝜔𝑐𝑐2
Ideal Zero Phase LPF • Ideal lowpass filter (unit magnitude, zero phase)
ℎ 𝑡𝑡 =sin(𝜔𝜔𝑐𝑐𝑡𝑡)
𝜋𝜋𝑡𝑡, 𝐻𝐻 𝑗𝑗𝜔𝜔 = �1, 𝜔𝜔 ≤ 𝜔𝜔𝑐𝑐
0, otherwise
• 𝒋𝒋𝒄𝒄: cutoff frequency
78
Simple RC Lowpass Filter • Differential Equation
𝑅𝑅𝑅𝑅𝑑𝑑𝑣𝑣𝑐𝑐 𝑡𝑡𝑑𝑑𝑡𝑡 + 𝑣𝑣𝑐𝑐 𝑡𝑡 = 𝑣𝑣𝑠𝑠(𝑡𝑡)
• Input 𝑣𝑣𝑠𝑠 𝑡𝑡 , output 𝑣𝑣𝑐𝑐 𝑡𝑡
• Taking Fourier transform 𝑗𝑗𝜔𝜔𝑅𝑅𝑅𝑅 ⋅ 𝑉𝑉𝑐𝑐 𝑗𝑗𝜔𝜔 + 𝑉𝑉𝑐𝑐 𝑗𝑗𝜔𝜔 = 𝑉𝑉𝑠𝑠(𝑗𝑗𝜔𝜔) • Frequency response:
𝐻𝐻 𝑗𝑗𝜔𝜔 =𝑉𝑉𝑐𝑐 𝑗𝑗𝜔𝜔𝑉𝑉𝑠𝑠 𝑗𝑗𝜔𝜔
=1
1 + 𝑗𝑗𝜔𝜔𝑅𝑅𝑅𝑅
79
Simple RC Lowpass Filter • Frequency response
𝐻𝐻 𝑗𝑗𝜔𝜔 =1
1 + 𝑅𝑅𝑅𝑅𝑗𝑗𝜔𝜔
|𝐻𝐻 𝑗𝑗𝜔𝜔 | =1
1 + 𝑅𝑅𝑅𝑅𝜔𝜔 2
arg𝐻𝐻(𝑗𝑗𝜔𝜔) = − arctan 𝑅𝑅𝑅𝑅𝜔𝜔
• Impulse response
ℎ 𝑡𝑡 =1𝑅𝑅𝑅𝑅
𝑒𝑒−𝑡𝑡/𝑅𝑅𝑅𝑅𝑢𝑢(𝑡𝑡)
• Nonideal lowpass filter ▫ passes lower frequencies ▫ attenuates higher frequencies
• Larger RC ⟹ passes smaller range of lower frequencies
80
• Ideal lowpass filter (unit magnitude, linear phase)
𝐻𝐻 𝑗𝑗𝜔𝜔 = �𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡0 , 𝜔𝜔 ≤ 𝜔𝜔𝑐𝑐
0, otherwise
⟹ |𝐻𝐻(𝑗𝑗𝜔𝜔)| = �1, |𝜔𝜔| ≤ 𝜔𝜔𝑐𝑐0, |𝜔𝜔| > 𝜔𝜔𝑐𝑐
, ≮ 𝐻𝐻(𝑗𝑗𝜔𝜔) = �−𝜔𝜔𝑡𝑡0 𝜔𝜔 ≤ 𝜔𝜔𝑐𝑐 0, otherwise
• 𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝑒𝑒−𝑗𝑗𝑗𝑗𝑡𝑡0𝑋𝑋𝐿𝐿𝐿𝐿 𝑗𝑗𝜔𝜔 ⟹ 𝑦𝑦 𝑡𝑡 = 𝑥𝑥𝐿𝐿𝐿𝐿(𝑡𝑡 − 𝑡𝑡0) ▫ Linear phase ⟺ simply a shift in time, no distortion ▫ Nonlinear phase ⟺ distortion in addition to time shift
Ideal Linear Phase LPF
81
𝜔𝜔𝑐𝑐 −𝜔𝜔𝑐𝑐
≮ 𝐻𝐻(𝑗𝑗𝜔𝜔) 𝜔𝜔𝑐𝑐𝑡𝑡0
−𝜔𝜔𝑐𝑐𝑡𝑡0
Example • Frequency response of an LTI system is
𝐻𝐻 𝑗𝑗𝜔𝜔 = �𝑗𝑗𝜔𝜔3𝜋𝜋
, 𝜔𝜔 ≤ 3𝜋𝜋
0, otherwise
• Considered as a cascade of an LPF and a differentiator
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𝑥𝑥(𝑡𝑡) 𝑦𝑦(𝑡𝑡) 𝐻𝐻2(𝑗𝑗𝜔𝜔) = 𝑗𝑗𝜔𝜔
𝐻𝐻(𝑗𝑗𝜔𝜔)
𝐻𝐻1(𝑗𝑗𝜔𝜔)
1/3𝜋𝜋
3𝜋𝜋 −3𝜋𝜋
• Dual of convolution property:
𝑥𝑥 𝑡𝑡 ⋅ 𝑦𝑦 𝑡𝑡 ℱ
12𝜋𝜋
[𝑋𝑋(𝑗𝑗𝜔𝜔) ∗ 𝑌𝑌(𝑗𝑗𝜔𝜔)]
multiplication in time ⟺ convolution in frequency
• Proof: let 𝑍𝑍 𝑗𝑗𝜔𝜔 = 12𝜋𝜋 ∫ 𝑋𝑋 𝑗𝑗𝜃𝜃 𝑌𝑌(𝑗𝑗(𝜔𝜔 − 𝜃𝜃))𝑑𝑑𝜃𝜃+∞
−∞
ℱ−1 𝑍𝑍 𝑗𝑗𝜔𝜔 =12𝜋𝜋
�12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜃𝜃 𝑌𝑌(𝑗𝑗(𝜔𝜔 − 𝜃𝜃))𝑑𝑑𝜃𝜃+∞
−∞𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔
+∞
−∞
=12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜃𝜃12𝜋𝜋
� 𝑌𝑌(𝑗𝑗(𝜔𝜔 − 𝜃𝜃))𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑑𝑑𝜔𝜔+∞
−∞𝑑𝑑𝜃𝜃
+∞
−∞
=12𝜋𝜋
� 𝑋𝑋 𝑗𝑗𝜃𝜃 𝑦𝑦 𝑡𝑡 𝑒𝑒𝑗𝑗𝜋𝜋𝑡𝑡𝑑𝑑𝜃𝜃 = 𝑥𝑥 𝑡𝑡 𝑦𝑦(𝑡𝑡)+∞
−∞
Multiplication Property
83
Example • Define a signal as
𝑥𝑥 𝑡𝑡 =sin 𝑡𝑡 ⋅ sin(𝑡𝑡/2)
𝜋𝜋𝑡𝑡2≜ 𝜋𝜋𝑥𝑥1 𝑡𝑡 𝑥𝑥2 𝑡𝑡
where,
𝑥𝑥1 𝑡𝑡 =sin 𝑡𝑡𝜋𝜋𝑡𝑡
𝑥𝑥2 𝑡𝑡 =sin(𝑡𝑡/2)
𝜋𝜋𝑡𝑡
• Fourier transform
𝑋𝑋 𝑗𝑗𝜔𝜔 =12𝑋𝑋1 𝑗𝑗𝜔𝜔 ∗ 𝑋𝑋2(𝑗𝑗𝜔𝜔)
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Example: Modulation Baseband signal: 𝑥𝑥 𝑡𝑡 Carrier:
𝑝𝑝 𝑡𝑡 = cos(𝜔𝜔𝑐𝑐𝑡𝑡) =12
(𝑒𝑒𝑗𝑗𝑗𝑗𝑐𝑐𝑡𝑡 + 𝑒𝑒−𝑗𝑗𝑗𝑗𝑐𝑐𝑡𝑡 )
𝑃𝑃 𝑗𝑗𝜔𝜔 = 𝜋𝜋𝛿𝛿 𝜔𝜔 − 𝜔𝜔𝑐𝑐 + 𝜋𝜋𝛿𝛿 𝜔𝜔 + 𝜔𝜔𝑐𝑐
• Modulated signal: 𝑦𝑦 𝑡𝑡 = 𝑥𝑥(𝑡𝑡)𝑝𝑝 𝑡𝑡
𝑌𝑌 𝑗𝑗𝜔𝜔 =12𝑋𝑋 𝑗𝑗(𝜔𝜔 − 𝜔𝜔𝑐𝑐) +
12𝑋𝑋 𝑗𝑗(𝜔𝜔 + 𝜔𝜔𝑐𝑐)
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Example: Demodulation • Modulated signal: 𝑦𝑦 𝑡𝑡 = 𝑥𝑥 𝑡𝑡 𝑝𝑝 𝑡𝑡
• Carrier: 𝑝𝑝 𝑡𝑡 = cos(𝜔𝜔𝑐𝑐𝑡𝑡)
• Demodulated signal: 𝑧𝑧 𝑡𝑡 = 𝑦𝑦 𝑡𝑡 𝑝𝑝 𝑡𝑡
𝑍𝑍 𝑗𝑗𝜔𝜔 =12𝑌𝑌 𝑗𝑗(𝜔𝜔 − 𝜔𝜔𝑐𝑐) +
12𝑌𝑌 𝑗𝑗(𝜔𝜔 + 𝜔𝜔𝑐𝑐)
=12𝑋𝑋 𝑗𝑗𝜔𝜔 +
14
[𝑋𝑋(𝑗𝑗 𝜔𝜔 − 2𝜔𝜔𝑐𝑐 ) + 𝑋𝑋(𝑗𝑗 𝜔𝜔 + 2𝜔𝜔𝑐𝑐 )] 𝑅𝑅 𝑗𝑗𝜔𝜔 = 𝑍𝑍 𝑗𝑗𝜔𝜔 𝐻𝐻lowpass(𝑗𝑗𝜔𝜔) 𝑥𝑥 𝑡𝑡 = 𝑟𝑟 𝑡𝑡
86
LCCDEs • Determine the frequency response of an LTI system described by
�𝑎𝑎𝑘𝑘𝑑𝑑𝑘𝑘𝑦𝑦(𝑡𝑡)𝑑𝑑𝑡𝑡𝑘𝑘
𝑁𝑁
𝑘𝑘=0
= �𝑏𝑏𝑘𝑘𝑑𝑑𝑘𝑘𝑥𝑥(𝑡𝑡)𝑑𝑑𝑡𝑡𝑘𝑘
𝑀𝑀
𝑘𝑘=0
• Method 1: using the eigenfunction property
let 𝑥𝑥 𝑡𝑡 = 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡 → 𝑦𝑦 𝑡𝑡 = 𝐻𝐻 𝑗𝑗𝜔𝜔 𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡
substitution in to the differential equation yields
�𝑎𝑎𝑘𝑘𝐻𝐻 𝑗𝑗𝜔𝜔 𝑗𝑗𝜔𝜔 𝑘𝑘𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑁𝑁
𝑘𝑘=0
= �𝑏𝑏𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑒𝑒𝑗𝑗𝑗𝑗𝑡𝑡𝑀𝑀
𝑘𝑘=0
𝐻𝐻 𝑗𝑗𝜔𝜔 =∑ 𝑏𝑏𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑀𝑀𝑘𝑘=0
∑ 𝑎𝑎𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑁𝑁𝑘𝑘=0
88
LCCDEs • Method 2: taking the Fourier transform of both sides
ℱ �𝑎𝑎𝑘𝑘𝑑𝑑𝑘𝑘𝑦𝑦(𝑡𝑡)𝑑𝑑𝑡𝑡𝑘𝑘
𝑁𝑁
𝑘𝑘=0
= ℱ �𝑏𝑏𝑘𝑘𝑑𝑑𝑘𝑘𝑥𝑥(𝑡𝑡)𝑑𝑑𝑡𝑡𝑘𝑘
𝑀𝑀
𝑘𝑘=0
• By linearity and differentiation in time property
�𝑎𝑎𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑌𝑌(𝑗𝑗𝜔𝜔) =𝑁𝑁
𝑘𝑘=0
�𝑏𝑏𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑋𝑋(𝑗𝑗𝜔𝜔) 𝑀𝑀
𝑘𝑘=0
𝐻𝐻 𝑗𝑗𝜔𝜔 =𝑌𝑌 𝑗𝑗𝜔𝜔𝑋𝑋(𝑗𝑗𝜔𝜔)
=∑ 𝑏𝑏𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑀𝑀𝑘𝑘=0
∑ 𝑎𝑎𝑘𝑘 𝑗𝑗𝜔𝜔 𝑘𝑘𝑁𝑁𝑘𝑘=0
• 𝐻𝐻 𝑗𝑗𝜔𝜔 is a rational function of (𝑗𝑗𝜔𝜔), i.e., ratio of polynomials
89
Example 𝑦𝑦′′ 𝑡𝑡 + 4𝑦𝑦′′ 𝑡𝑡 + 3𝑦𝑦 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 + 2𝑥𝑥(𝑡𝑡)
• Frequency response
𝐻𝐻 𝑗𝑗𝜔𝜔 =𝑗𝑗𝜔𝜔 + 2
𝑗𝑗𝜔𝜔 2 + 4 𝑗𝑗𝜔𝜔 + 3
▫ Using partial fraction expansion
𝐻𝐻 𝑗𝑗𝜔𝜔 =𝑗𝑗𝜔𝜔 + 2
𝑗𝑗𝜔𝜔 + 1 (𝑗𝑗𝜔𝜔 + 3)=
𝐴𝐴1𝑗𝑗𝜔𝜔 + 1
+𝐴𝐴2
𝑗𝑗𝜔𝜔 + 3
▫ Let 𝑣𝑣 = 𝑗𝑗𝜔𝜔
𝐴𝐴1= 𝑣𝑣 + 1 𝐻𝐻 𝑣𝑣 �𝑣𝑣=−1
=12
,𝐴𝐴2 = 𝑣𝑣 + 3 𝐻𝐻 𝑣𝑣 �𝑣𝑣=−3
=12
▫ Taking inverse Fourier transform to find impulse response
ℎ 𝑡𝑡 =12𝑒𝑒−𝑡𝑡 +
12𝑒𝑒−3𝑡𝑡 𝑢𝑢 𝑡𝑡
90
Example 𝑦𝑦′′ 𝑡𝑡 + 4𝑦𝑦′′ 𝑡𝑡 + 3𝑦𝑦 𝑡𝑡 = 𝑥𝑥′ 𝑡𝑡 + 2𝑥𝑥(𝑡𝑡)
• Determine zero-state response to 𝑥𝑥 𝑡𝑡 = 𝑒𝑒−𝑡𝑡𝑢𝑢 𝑡𝑡
𝑌𝑌 𝑗𝑗𝜔𝜔 = 𝐻𝐻 𝑗𝑗𝜔𝜔 𝑋𝑋 𝑗𝑗𝜔𝜔 =𝑗𝑗𝜔𝜔 + 2
𝑗𝑗𝜔𝜔 + 1 𝑗𝑗𝜔𝜔 + 3 ⋅1
𝑗𝑗𝜔𝜔 + 1=
𝐴𝐴1,1𝑗𝑗𝜔𝜔 + 1 +
𝐴𝐴1,2𝑗𝑗𝜔𝜔 + 1 2 −
𝐴𝐴2𝑗𝑗𝜔𝜔 + 3
▫ Using partial fraction expansion, let 𝑣𝑣 = 𝑗𝑗𝜔𝜔
𝐴𝐴1,1=1
2 − 1 !𝑑𝑑𝑑𝑑𝑣𝑣
𝑣𝑣 + 1 2𝑌𝑌 𝑣𝑣 �𝑣𝑣=−1
=𝑑𝑑𝑑𝑑𝑣𝑣
𝑣𝑣 + 2𝑣𝑣 + 3
�𝑣𝑣=−1
=14
𝐴𝐴1,2= 𝑣𝑣 + 1 2𝑌𝑌 𝑣𝑣 �𝑣𝑣=−1
=12
,𝐴𝐴2 = 𝑣𝑣 + 3 𝑌𝑌 𝑣𝑣 �𝑣𝑣=−3
= −14
▫ Taking inverse Fourier transform to find output
𝑦𝑦 𝑡𝑡 =14𝑒𝑒−𝑡𝑡 +
12𝑡𝑡𝑒𝑒−𝑡𝑡 −
14𝑒𝑒−3𝑡𝑡 𝑢𝑢 𝑡𝑡
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