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Rev 1.0AN2242/1205 1/31
31
AN2242APPLICATION NOTE
Reference design: high performance, L6668-based flybackconverter for Set-Top boxes and PVRs
IntroductionThis document describes a reference design of a 40W Switch Mode Power Supply dedicated to Set-Top box application. The board accepts wide range input voltage (90 to 265Vrms) and delivers 4 outputs. It is based on the new controller L6668, working in PWM fixed frequency current mode. High efficiency and low standby consumption are the main characteristics of this board. Such features, coupled with the minimal part count required and the global solution low cost approach, makes it an ideal solution for powering digital consumer equipment, meeting worldwide standby rules.
Figure 1. EVAL6668-STB Demo Board, Described In This Application Note
www.st.com
AN2242
2/31
Contents
1 Main Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
2 Circuit Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
3 Cross Regulation and Standby . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
4 Functional Checking . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
4.1 Start-up Behaviour at Full Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
4.2 Wake-up Time . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
4.3 Power-down . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
4.4 Short-Circuit Tests . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
4.5 Over Voltage Protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19
5 Conducted Noise Measurements (Pre-Compliance Test) . . . . . . . . . . . . 21
6 Thermal Measures . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22
7 Part List . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23
8 PCB Layout . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27
9 Transformer Specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28
9.1 Electrical Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28
9.2 Mechanical Aspect . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29
9.3 Manufacturer . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29
10 Revision History . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 30
AN2242
3/31
Figures
Figure 1. EVAL6668-STB Demo Board, Described In This Application Note. . . . . . . 1Figure 2. Electrical Diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6Figure 3. Vin = 115 Vrms - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8Figure 4. Vin = 230 Vrms - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8Figure 5. Vin = 265 Vrms - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8Figure 6. Vin = 115 Vrms - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9Figure 7. Vin = 220 Vrms - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9Figure 8. Vin = 230 Vrms - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10Figure 9. Input Power vs. Mains Voltage During Standby . . . . . . . . . . . . . . . . . . . . 13Figure 10. Pin at 230vac vs. Iout 5V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14Figure 11. Vin = 230 Vrms - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14Figure 12. Vin = 90 VAC - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15Figure 13. Vin = 265 VAC - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15Figure 14. at 115 VAC - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16Figure 15. at 230 VAC - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16Figure 16. at 115 VAC - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17Figure 17. at 230 VAC - 50Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17Figure 18. 12V OUTPUT SHORT at 90 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18Figure 19. 3.3V OUTPUT SHORT at 265 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18Figure 20. 3.3V OUTPUT SHORT at 265 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18Figure 21. 5V OUTPUT SHORT at 265 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18Figure 22. 1.8V OUTPUT SHORT at 90 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19Figure 23. 1.8V OUTPUT SHORT at 265 VAC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19Figure 24. OVP at 115 VAC - 60Hz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20Figure 25. Conducted Noise Measurements - Phase A . . . . . . . . . . . . . . . . . . . . . . . 21Figure 26. Concucted Noise Measurements - Phase B . . . . . . . . . . . . . . . . . . . . . . . 21Figure 27. 115Vac-Max Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22Figure 28. 230Vac-Max Load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22Figure 29. Silk Screen -Top Side . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27Figure 30. Silk Screen -Bottom Side . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27Figure 31. Copper Tracks. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27Figure 32. Transformer Electrical Diagram. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28Figure 33. Winding Position . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29
AN2242
4/31
Tables
Table 1. Output Voltages. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5Table 2. Output Voltage Measurement at Full Load . . . . . . . . . . . . . . . . . . . . . . . . 11Table 3. Output Voltage Measurement at HDD SPIN-UP . . . . . . . . . . . . . . . . . . . 11Table 4. Output Voltage Measurement at Reduced, W/O HDD . . . . . . . . . . . . . . . 12Table 5. Output Voltage Measurement at Minimum Load. . . . . . . . . . . . . . . . . . . . 12Table 6. Output Voltage Measurement at Standby Load . . . . . . . . . . . . . . . . . . . . 13Table 7. Part List . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23Table 8. Winding Characteristics. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29
AN2242 1 Main Characteristics
5/31
1 Main Characteristics
The main characteristics of the SMPS are listed here below:
INPUT VOLTAGE:
- Vin: 90 - 264 Vrms
- f: 45-66Hz
OUTPUT VOLTAGES:
Table 1. Output Voltages
STANDBY: Below 1W with 5V at 50mA residual load
SHORT CIRCUIT PROTECTION: On all outputs, with auto-restart at short removal
PCB TYPE & SIZE: Single Side 70um (2-Oz), CEM-1, 150 x 75mm
SAFETY: Acc. to EN60065, creepage and clearance minimum distance 6.4mm
EMI: Acc. to with EN50022-Class B
Vout IoutMAX IoutMIN PMAX STABILITY NOTES
1.8V 1.73A 0.20A 3.1W ±7%Dedicated to digital circuitry and to 1.2V local post regulators
3.3V 0.5A 0.03A 1.65W ±5%Dedicated to analog peripherals and 2.5V regulators
5V 2.4A 0.3A 12W ±10% Dedicated to HDD and 5V circuitry
12V1.9Avg2.9Apk
0.05A 34.8W ±8%
Dedicated to HDD, SCART, LNBP21 for satellite STB.Average load is 1.9A, 2.9A is dedicated to HDD spin-up
POUT(W)=40WAVG / 51Wpk
1 Main Characteristics AN2242
6/31
Figure 2. Electrical Diagram
g
R20
1K8
R23
1K0
R24
1K0
C37
3N3
C32
100N
C24
220u
F-16
V Y
XF
1 2
4 3
U3
SFH
617A
-4
C9
470u
F-25
V Y
XF
L2
2.7u
H
C28
100u
F-25
V
+3V
3
@0.5
A
C11
100u
F-25
V Y
XF
D9
STP
S1L
60A
D12
1N58
21
C35
2200
uF-1
6V Y
XF
C29
100u
F-25
V
+1V
8
@1.7
A
L3
2.7u
H
C22
1000
uF-1
6V Y
XF
C27
100u
F-25
V
+5V
@2.4
A
L4
22uH
C10
470u
F-25
V Y
XF
C14
100N
C15
100N
C17
100N
C12
100N
+12
V
R4
4K7
R25
3K3
R26
1K0
C21
10N
-400
V
R7
33K
-2W
R1
NT
C_1
0R S
236
F1 FUSE
2A
C18
220N
-X2
90-2
64V
rms
C20
82uF
-400
V
C30
2N2
Q1
STP
4NK
60Z
FP
R8
33R
R17
82R R
161K
0
C34
220P
C16
100N
C31
100N
R15
6K2
C33
10N
C19
47uF
-50V
R5
470K
R6
330K
R22
27K
R21
3K9
C36
470P
R12
10K
R13
36K
R19
0R47
R18
0R47
341
2
L1
HF2
430-
203Y
1R0-
T01
TD
K
D5
BA
V10
3
4
1
3
2
D1
2W06
G
D6
BA
V10
3
D7
STT
H1L
06U C5
2N2
- Y
1
T1
SRW
28L
EC
-E01
1 2
J1 INP
UT
CO
NN
.
HS1
C39
100N
C38
100N
1 3 5 6
@1.9
A-2
.9A
pk
L5
2.7u
H
D2
STP
S8H
100F
P
C23
1000
uF-1
6V Y
XF
R10
10K
C7
1N0
R2
3R9
R14
30K
R27
5K6
SKIP
AD
J9
ISE
N12
HVS(nc)2
HV1 O
UT
4
VR
EF
8
RC
T16
VC
C5
S_C
OM
P15
PFC_STOP14
ST-B
Y13
GN
D3
SS11
N.C
.6
OVP7
COMP10
U2
L6668
D10
STP
S10L
60FP
1 2 3 4 5 6 7 8J2 O/P
CO
NN
+1V
8
+5V
+12
V
+3V
3
D13
LL
4148
Q2
BC
847B
Q3
BC
847B
R30
270R
R29
10K
R28
1K
R34
1K0
R33
1K0
R32
1K0
R35
1K0
78910
11
12
U4
TS2
431I
LT
C41
2
HS2
HS3
L28
5
C41
10uF
-50V
D16
LL
4148
R36 3K
3
C40
10uF
-50V
Q5
BC
847B
Q4
BC
857B
DIS
AN2242 2 Circuit Description
7/31
2 Circuit Description
The topology used in this schematic is a classical flyback, working in continuous and discontinuous conduction mode with fixed frequency, achieves the best tradeoff between peak/rms current ratio and the output capacitors' size. The nominal switching frequency, 65kHz, has been chosen to get a compromise between the transformer size and the harmonics of the switching frequency, optimizing the input filter size and its cost. The input EMI filter is a classical Pi-filter, 1-cell for differential and common mode noise. A NTC limits the inrush current produced by the capacitor charging at plug-in. The MOSFET is a standard and cheap 600V-2Ω max, TO-220FP, needing a small heat sink. The transformer is a layer type, using a standard ferrite type EER28L. The transformer, designed according to the EN60065, is manufactured by TDK. The reflected voltage is 70V, providing enough room for the leakage inductance voltage spike with still margin for reliability of the MOSFET. The network D7, R7, C21 clamps the peak of the leakage inductance voltage spike. The controller is the new L6668, integrating all the functionalities needed to control an SMPS with high performance and minimum component count, offering the maximum flexibility. A new functionality embedded in the device is a high-voltage current source used at start-up that draws current from the DC bus and charges the capacitor C19. After the voltage on C19 has reached the L6668 turn-on threshold and the circuit starts to operate, the controller is powered by the transformer via the diode D5. After the start-up, the HV current source is deactivated, saving power during normal operation and allowing very good circuit efficiency during standby. The control system is Current Mode, so the current flowing in the primary is sensed by R18 and R19 and is then fed into pin #12 (Isen). R5 and R6 are also connected to pin #12 (Isen). Their purpose is to compensate the power capability change vs. the input voltage. The resistor R27 connected between pin #12 (Isen) and pin #15 (S_Comp) provides the correct slope compensation to the current signal, necessary for the correct loop stability. The circuit connected to pin #7 (DIS) provides over voltage protection in case of feedback network failures and open loop operation. An internal comparator senses this pin voltage and in case its threshold is exceeded the L6668 stops operating and reduces its consumption. To definitely latch this state an internal circuitry of the L6668 monitors the Vcc periodically reactivates the HV current source to supply the IC. After OVP detection and Disable intervention the controller operation can be resumed only after disconnecting the mains plug. The switching frequency is programmed by the RC connected to pin #16 (RCT) and in case of reduced load operation the controller can decrease the operating frequency via the pin #13 (ST-BY) and resistor R15, proportionally to the load consumption. The resistor dividers R13 and R14 connected to pin #9 (SKIPADJ) allow to set the initial L6668 threshold to burst mode functionality when the power supply is lightly loaded. Additional functions embedded in the L6668 are the programmable soft-start and a 5V reference available externally. The output rectifiers have been selected according to the calculated maximum reverse voltage, forward voltage drop and power dissipation. The rectifiers for 5V and 12V outputs are Schottky, low forward voltage drop type, hence they dissipate less power with respect to standard types. A small heat sink for both devices is required, as indicated on the BOM. The other two output rectifiers are Schottky too but with a smaller package. The snubber made up of R2 and C7 damps the oscillation produced by the diode D2 at MOSFET turn-on. The output voltage regulation is performed by secondary feedback on the 12V, 5V and 3.3V output, while for the 1.8V output the regulation is achieved by the transformer coupling. The feedback network uses a TS2431 driving an optocoupler, in this case a SFH617A-4, ensuring the required insulation between primary and secondary. The opto-transistor drives directly the COMP pin of the L6668. A small LC filter has been added on all outputs in order to filter the high frequency ripple without increasing the output capacitors and a 100nF capacitor has been placed on each output, very close to the output connector solder points, to limit the spike amplitude.
2 Circuit Description AN2242
8/31
Here follow some waveforms during normal operation at full load:
The pictures above show the drain voltage and current signal on pin #12 at the nominal input mains voltage during normal operation at full load. The Envelope acquisition of the scope provides for the possibility to observe the modulation of the two waveforms, due to the mains input voltage ripple at twice the line frequency.
Figure 5. The drain voltage waveforms and the measurement of the peak voltage at full load and maximum input mains voltage are shown. The maximum voltage peak in this condition is 524V, which ensures a reliable operation of the power MOSFET with a good margin against the maximum BVDSS. The operation during the hard-disk spin-up when the SMPS delivers the peak power to the loads, brings the drain voltage peak at 540Vpk.
Figure 5. Vin = 265 Vrms - 50Hz
Figure 5. and Figure 6. depict the most salient controller IC signals. In all pictures it is possible to distinguish clean waveforms free of hard spikes or noise that could affect the controller
Figure 3. Vin = 115 Vrms - 60Hz Figure 4. Vin = 230 Vrms - 50Hz
CH1: DRAIN VOLTAGECH2: DRAIN CURRENT - VPIN12 (Isen)
CH1: DRAIN VOLTAGECH2: DRAIN CURRENT - VPIN12 (Isen)
CH1: DRAIN VOLTAGECH2: DRAIN CURRENT - VPIN12 (Isen)
AN2242 2 Circuit Description
9/31
correct operation. More precisely, in Figure 5. and Figure 6. the waveforms during normal operation at max load and both nominal input mains voltage measured on current sense pin, gate drive, comp and oscillator pin have been captured. It is possible to notice that the circuit works in continuous over the entire input mains range.. Besides, the signal on pin #12 (Isen), has a different offset and similar peak for the effect of R5 and R6. Their purpose is in fact to compensate the over current set point variation with the input voltage, which instead has to be almost constantover the entire input voltage mains range. Of course, the oscillator waveform does not change in the two pictures.
In Figure 8. channel 4 shows the slope compensation signal, coming from pin #15. This pin provides a voltage ramp during the MOSFET's ON-time, which is a repetition of the oscillator saw tooth and is dedicated to implementing additive slope compensation on current sense. This is needed to avoid the sub-harmonic oscillation that arises in all peak-current-mode-controlled converters working in continuous conduction mode with a duty cycle close to or exceeding 50%, as in this circuit. Besides, only a resistor is needed to implement slope compensation, and since the voltage ramp is delivered during the ON-time only, the correct operation of the control circuit is ensured even at light load. The slope compensation signal delivered only during ON-time in fact prevents perturbations on the current sense due to the injection of the residual part of the oscillator saw tooth that could affect the control circuit, as it happens using the oscillator total saw tooth for slope compensation.
Figure 6. Vin = 115 Vrms - 60Hz Figure 7. Vin = 220 Vrms - 50Hz
CH1: VPIN12 - ISENCH2: VPIN4 - OUTCH3: VPIN16 - RCTCH4: VPIN10 - COMP
CH1: VPIN12 - ISENCH2: VPIN4 - OUTCH3: VPIN16 - RCTCH4: VPIN10 - COMP
2 Circuit Description AN2242
10/31
Figure 8. Vin = 230 Vrms - 50Hz
CH1: VPIN12 - ISENCH2: VPIN4 - OUTCH3: VPIN16 - RCTCH4: VPIN15 - S_COMP
AN2242 3 Cross Regulation and Standby
11/31
3 Cross Regulation and Standby
The following tables show the output voltage measurements and the overall efficiency of the converter measured at different input voltages. All the output voltages have been measured on the output connector.
Table 2. Output Voltage Measurement at Full Load
Table 2. lists the output voltage measurements at both nominal mains range: all voltages are within the tolerance given in the specification. The efficiency measured is very good for this kind of SMPS, thanks to the absence of post regulators.
Table 3. shows the same measurement done during the HDD spin-up, which means higher current from the 12V output, while the other output currents are not changed.
Table 3. Output Voltage Measurement at HDD SPIN-UP
As clearly visible in this table, the output voltages are still within the given tolerance. The heavier load does not affect efficiency. Please note that that the total output power of Table 3. is the so-called "electrical power", not the "thermal power". Therefore, the circuit has been designed to deliver the "electrical power" for a short time only - typically the HDD spin-up has
at 115Vac - 60Hz at 230Vac - 50Hz
Voltage [V] Current [A] Deviation Voltage [V] Current [A] Deviation
11.70 1.9 -2.50% OK 11.6 1.9 -3.33% OK
1.81 1.7 0.56 OK 1.82 1.7 1.11% OK
4.82 2.4 -3.60% OK 4.82 2.4 -3.60% OK
3.28 0.5 -0.61% OK 3.28 0.5 -0.61% OK
at 115Vac - 60Hz at 230Vac - 50Hz
Voltage [V] Current [A] Deviation Voltage [V] Current [A] Deviation
11.51 2.9 -4.08% OK 11.46 2.9 -4.50% OK
1.81 1.7 0.56% OK 1.82 1.7 1.11% OK
4.77 2.4 -4.60% OK 4.80 2.4 -4.00% OK
3.3 0.5 -0.00% OK 3.29 0.5 -0.30% OK
Vin= 115Vac
lin= 0.75Arms
Pin= 49W
EFF.= 78.6%
Vin= 230Vac
lin= 0.44Arms
Pin= 47.6W
EFF.= 80.6%
Pout=38.52W Pout=38.34W
Vin= 115Vaclin= 0.93Arms
Pin= 64.5WEFF.= 76.8%
Vin= 230Vaclin= 0.55ArmsPin= 61.2W
EFF.= 80.9%
Pout=49.55W Pout=49.49W
3 Cross Regulation and Standby AN2242
12/31
duration of 1 second - but it cannot be delivered significantly longer because, from the thermal point of view, the circuit can manage the full load only with the required reliability. The board has been designed to power a digital decoder equipped with a hard disk drive but it can be used even for powering a Set-Top box without the Hard disk drive. The measurements shown in Table 4. are relevant to a load condition typical of a satellite Set-Top box. The 12V and 5V loads have been reduced with respect to the previous measurements.
Table 4. Output Voltage Measurement at Reduced, W/O HDD
At minimum load the power supply is still capable of keeping the output voltages regulated within the specification, as indicated by the measurements in Table 5. Additionally, the auxiliary voltage has been measured too: note that the voltage powering the IC has a good margin with respect to the L6668 turn-off voltage.
Table 5. Output Voltage Measurement at Minimum Load
at 115Vac - 60Hz at 230Vac - 50Hz
Voltage [V] Current [A] Deviation Voltage [V] Current [A] Deviation
11.86 1.1 -1.17% OK 11.76 1.1 -2.00% OK
1.79 1.7 -0.56% OK 1.81 1.7 0.56% OK
4.85 1.8 -3.00% OK 4.9 1.8 -2.00% OK
3.27 0.5 -0.91% OK 3.26 0.5 -1.21% OK
Pout= 26.45 W Pout= 26.46 W
at 115Vac - 60Hz at 230Vac - 50Hz
Voltage [V] Current [A] Deviation Voltage [V] Current [A] Deviation
11.72 0.05 -2.33% OK 11.65 0.05 -2.92% OK
1.80 0.2 0.00% OK 1.80 0.2 0.00% OK
4.77 0.3 -4.600% OK 4.78 0.3 -4.40% OK
3.35 0.03 1.52% OK 3.34 0.03 1.21% OK
Vin= 115Vaclin= 0.48ArmsPin= 33.1WEFF.= 79.9%
Vin= 230Vaclin= 0.29ArmsPin= 33.4W
EFF.= 79.2%
Pout=26.45W Pout=26.45W
Vin= 115Vac
lin= 0.082Arms
Pin= 3.6W
Vaux=1.5V
EFF.= 68.8%
Vin= 230Vac
lin= 0.05Arms
Pin= 4.2W
Vaux=11.4V
EFF.= 59.0%
Pout=2.48W Pout=2.48W
AN2242 3 Cross Regulation and Standby
13/31
Table 6. Output Voltage Measurement at Standby Load
In Table 6. the output voltage measurements during standby operation are shown. Even in this load condition the circuit is able to regulate the output voltages within the required tolerance.
Figure 9. Input Power vs. Mains Voltage During Standby
It is clearly visible that, while delivering the required standby load, (5V at 50mA, 1.8V, 3.3V and 12V at 0mA) the input power consumption is below 800mW at both the nominal input voltage ranges and remains below 900mW at 265Vac. Figure 10. represents the input power variation as a function of the 5V current.
During the standby operation the circuit works in burst mode, thus the number of switching cycles decreases and, therefore it brings to an equivalent continuous switching frequency reduction. This minimizes all frequency-related losses and maximizes the efficiency with respect to other controllers without this feature. The L6668 enters automatically in burst mode when its internal circuitry detects a light load by monitoring the voltage on pin #10 (Comp). When it falls by 50mV below the threshold programmed via the divider connected at to pin #9 (SKIPADJ), the IC is disabled and its consumption is reduced to minimize the Vcc capacitor discharge. The soft-start capacitor is not discharged. The control voltage now will increase as a result of the feedback reaction to the energy delivery stop, the threshold will be exceeded and the IC will restart switching again. In this way the converter works in burst-mode with a constant
at 115Vac - 60Hz at 230Vac
Voltage [V] Current [A] Deviation Voltage [V] Current [A] Deviation
11.80 0 -1.67% OK 11.70 0 -2.50% OK
1.92 0 6.67% OK 1.92 0 6.67% OK
4.71 0.047 -5.80% OK 4.73 0.047 -5.40% OK
3.36 0 1.82% OK 3.36 0 1.82% OK
Vin= 115Vaclin= 0.017Arms
Pin=0.51WVaux=9.68V
EFF.= 43.5%
Vin= 230Vaclin= 0.0217Arms
Pin=0.75WVaux=10V
EFF.= 29.8%
Pout=0.22W Pout=0.22W
00.10.20.30.40.50.60.70.80.9
1
Mains voltage
Inp
ut p
ow
er
Pin= [W] 0.49 0.51 0.75 0.88
Vaux= [V] 9.67 9.68 10 10.04
90Vac 115Vac 230Vac 265Vac
3 Cross Regulation and Standby AN2242
14/31
peak current defined by the disable level applied at to pin #9. This functionality is well visible in Figure 11., where the most significant waveforms are depicted during the standby operation. It is possible to check that the circuit stops switching as soon as the COMP pin voltage is equal to the SKIPADJ voltage and restarts to operate as soon as the threshold returns at the same level with the mentioned voltage histeresys. In the above table also the auxiliary voltage measurement is shown. At minimum load the value is still enough to ensure correct operation of the L6668 with margin. During standby operation the output voltages are only affected by a slight ripple at burst frequency, due to the operation of the internal control comparator. The ripple peak to peak measured in worst case at 265Vac on the 5V output was 68mV.
Figure 10. Pin at 230vac vs. Iout 5V
Figure 11. Vin = 230 Vrms - 50Hz
Pin @230vac vs. Iout 5V
0
0.2
0.4
0.6
0.8
1
1.2
1.4
20 30 40 50 60 70 80Iout 5V [mA]
Pin
@23
0vac
[W]
CH1: VDRAINCH2: VPIN10- COMP
CH3: VPIN16 - RCTCH4: VPIN9 - SKIP_ADJ
AN2242 4 Functional Checking
15/31
4 Functional Checking
4.1 Start-up Behaviour at Full Load
Figure 12. and Figure 13. capture the rising slopes at full load of output voltages at minimum and maximum input mains voltage. As shown in the pictures, the rising times are constant and there is no difference between the rise time of the output voltages. To avoid problems at start-up, this characteristic is quite important when the loads are a microprocessor and its peripherals, as in our case. Just a negligible overshoot is present at both mains voltages, without consequences for the supplied circuitry. The soft start time can be programmed via the soft-start capacitor connected to pin #11 of the L6668.
4.2 Wake-up Time
The wake-up time is the time needed for the power supply to deliver the nominal output voltages once it has been plugged-in or, if there is any, the mains switch has been closed. Generally, with wide mains power supplies using passive solutions for start-up like the largest part on the market, it is difficult to find a good compromise between the wake-up time at low mains, the dissipation at high mains and the circuit complexity. The following figures show the waveforms with the wake-up time measurements at both nominal input mains. The measured wake-up time at 115Vac and 230Vac is 750millisecond, which is a common value for this kind of power supplies. Thus, thanks to high voltage circuitry integrated in the L6668, the wake-up time is perfectly constant vs. the input voltage, which can be achieved without any external component or special circuitry. Moreover, as soon as the IC has started, the HV current source is switched off, saving power that would affect the efficiency and the standby performance of the SMPS otherwise.
Figure 12. Vin = 90 VAC - 60Hz Figure 13. Vin = 265 VAC - 50Hz
CH1: +12 VoutCH2: +5 Vout
CH3: +3.3 VoutCH4: +1.8 Vout
4 Functional Checking AN2242
16/31
To avoid spurious start-up attempts when power supply is plugged in with abnormal, lower voltage mains, the HV current source has a turn-on threshold so that it is not activated if the input voltage is lower than the Start voltage (typ. value is 80V).
As visible in Figure 14. and Figure 15. captured at the nominal mains voltages there is not any overshoot, undershoot, dip or abnormal behaviour during the power supply start-up phase. The power supply has been checked over the entire input voltage range with same positive results as in the above figures.
4.3 Power-down
Even at turn off the transition is clean, without any abnormal behaviour like restart or glitches on both the auxiliary and the output voltages. This is still provided by the HV start-up circuitry that controls the power down sequence: at converter power-down the system loses regulation, then Vcc drops and IC activity is stopped as it falls below the UVLO threshold (8.7V typ.). To prevent restart attempts of the converter and to ensure monotonic output voltage decay at power-down an internal logic re-enables the HV current source only if the Vcc voltage goes below the threshold Vccrest located at about 5V. Thus, the HV generator can restart but, if Vin is lower than Vinstart, the HV generator is disabled.
Figure 16. and Figure 17. also the hold-up time at both nominal mains voltages is measured 115 Vac the input Elcap stores enough energy to keep the regulation for 20mS at full load. After that the converter loses regulation and the output voltages drop. The measured time is enough to provide the required immunity of the Set-Top box against standard mains dip or short interruptions tests, required by the standard rules such as the IEC1000 and protecting the unit
Figure 14. at 115 VAC - 60Hz Figure 15. at 230 VAC - 50Hz
CH1: VDDCH2: VC19 (Vaux)
CH3: +12 VoutCH4: +1.8 Vout
AN2242 4 Functional Checking
17/31
against lost of channel tuning or video disturbances while the end user is watching TV or recording programs.
4.4 Short-Circuit Tests
An important functionality of any power supply is the capability to survive in case of load short circuit and to avoid any consequent failure. Additionally, the power supply must be compliant with safety rules, which require that, in case of fault, no component will melt or burn-out. The SMPS protection is another issue of power supplies. Sometimes it is easy to find circuits with good protection capability against shorts of the load but which are not able to survive in case of a very hard short like that of an output electrolytic capacitor or of a rectifier or transformer saturation. Besides, in case of a shorted rectifier the equivalent circuit changes and the energy is delivered even during the on time, as in forward mode. In case of a short, the voltage at pin Isen exceeds the VISENdis threshold (Hiccup-mode OCP level) and the controller stops the operation, so avoiding the destruction of the components at primary side. The controller remains in off-state until the voltage across the Vcc pin decreases below the UVLO threshold. It will then try to restart without success until the secondary short is removed. This provides a low frequency hic-cup working mode, preventing the power supply from being destroyed.
The board has been tested over the entire input voltage mains range. Two critical circuit parameters, the Vds and the output current have been checked during short circuit tests. In all conditions the measured drain voltage is always below the BVDSS, while the mean value of the output current has a value lower or close to the nominal one, therefore preventing the component damage. As indicated by the waveforms in Figure 18. and Figure 19., once an output is shorted, the circuit begins to work in hic-cup mode, keeping the mean value of the current at levels sustainable by the component rating. Because the working time and the dead time are imposed by the charging and discharging time of the auxiliary capacitor C19, thanks to the L6668 current source and related circuitry, the on-off periods are independent from the input mains voltage, contrary to controller using a passive start-up circuitry where the on time
Figure 16. at 115 VAC - 60Hz Figure 17. at 230 VAC - 50Hz
CH1: VDDCH2: VC19 (Vaux)
CH3: +12 VoutCH4: +1.8 Vout
4 Functional Checking AN2242
18/31
duration increases significantly with the mains voltage. The auto-restart at short removal is correct in all conditions.
Figure 20. and Figure 21. show the short circuit waveforms shorting the 3.3V and the 5V output. Like the 12V output voltage the controller keeps under control the circuit preventing in all conditions the power supply from catastrophic failures. Even the 1.8V output is well protected against shorts, in fact figures Figure 22. and Figure 23. are relevant to a short at minimum and maximum mains voltage. Because the coupling between the 1.8V and the auxiliary windings is poor, to help the circuit enter in burst mode the circuitry based on Q2 and
Figure 18. 12V OUTPUT SHORT at 90 VAC Figure 19. 3.3V OUTPUT SHORT at 265 VAC
Figure 20. 3.3V OUTPUT SHORT at 265 VAC Figure 21. 5V OUTPUT SHORT at 265 VAC
CH1: DRAIN VOLTAGECH2: VPIN12(Vcc)
CH3: 12 VoutCH4: ISHORT CIRCUIT
CH1: DRAIN VOLTAGECH2: VPIN12(Vcc)
CH3: 3.3 VoutCH4: ISHORT CIRCUIT
CH1: DRAIN VOLTAGECH2: VPIN12(Vcc)
CH3: 5 VoutCH4: ISHORT CIRCUIT
AN2242 4 Functional Checking
19/31
Q3 has been added. This circuit senses the output voltage and drive the circuit to work in hic-cup mode if the 1.8V output voltage disappears
4.5 Over Voltage Protection
A protection that all power supplies must have is that against the failure of the feedback circuitry. If this occurs, the SMPS output voltages can get high values, depending on the load on each output and the transformer coupling between the windings. Consequently, the rectifiers and the output capacitors are overstressed and they can be destroyed. To avoid this SMPS failure, a dedicated low-cost circuit has been added that senses the auxiliary voltage, thus providing a protection threshold not as dependent on the mains voltage or the load. This signal is connected to the L6668, pin 7 (DIS), dedicated to a latched protection of the circuit, as needed to properly protect the power supply from OVP or OTP. The IC pin #7 is the non-inverting input of a comparator having the inverting input internally referenced to 2.2V (typ.). As the voltage on the pin exceeds the threshold, the L6668 stops the operation and its consumption is reduced to a low value. The status is latched until the Vcc goes below the UVLO threshold. To remain in the latch status, the L6668 internal HV generator is activated periodically so that the Vcc oscillates between the start-up threshold VccON and VccON - 0.5V. The SMPS can restart after the disconnection of the converter from the mains and the Vcc pin decreases below the UVLO threshold. Figure 24. depicts the circuit behaviour described above. During a feedback loop failure, the board OVP circuitry voltage intervention threshold allows the 12V output to rise up to 16.8V at 115Vac, and doesn't change significantly with the input voltage or the load.
Figure 22. 1.8V OUTPUT SHORT at 90 VAC Figure 23. 1.8V OUTPUT SHORT at 265 VAC
CH1: DRAIN VOLTAGECH2: VPIN12(Vcc)
CH3: 1.8 VoutCH4: ISHORT CIRCUIT
4 Functional Checking AN2242
20/31
Figure 24. OVP at 115 VAC - 60Hz
CH1: VPIN7 (OVP)CH2: VC19(Vaux)CH3: +12 Vout
AN2242 5 Conducted Noise Measurements (Pre-Compliance Test)
21/31
5 Conducted Noise Measurements (Pre-Compliance Test)
The following pictures are the conducted noise measurements at full load and 230Vac mains voltage, made on phase and neutral line with Peak detection. The limits shown in the diagrams are the EN55022 CLASS B ones, which is the most common rule for video domestic equipments, such as Set-Top boxes. As clearly visible in the diagrams there is a good margin of the measures with respect to the limits.
Figure 25. Conducted Noise Measurements - Phase A
Figure 26. Concucted Noise Measurements - Phase B
6 Thermal Measures AN2242
22/31
6 Thermal Measures
In order to check the design reliability, a thermal mapping by means of an IR Camera was done. Here below the thermal measures of the component board side at nominal input voltage are shown. Some pointers visible on the pictures have been placed across key components or components showing high temperature. The correlation between measurement points and components is indicated on the right of both figures.
TAMB = 28 degC for all measures
Figure 27. 115Vac-Max Load
Figure 28. 230Vac-Max Load
The thermistor, bridge and output diodes temperature rise are compatible with the reliable operation of the components. Resistor R7 may need a bigger package to decrease its thermal resistance. All other components of the board are working within the temperature limits assuring a reliable long term operation of the power supply.
A 83.70°C E= 0.95 R1 (NTC) B 58.29°C E= 0.95 D1 (BRIDGE) C 116.60°C E= 0.95 R7 (CLAMP) D 75.67°C E= 0.95 T1 (WINDING) E 73.64°C E= 0.95 T1 (FERRITE) F 98.34°C E= 0.95 D2 G 73.85°C E= 0.95 D10 H 69.91°C E= 0.95 D12
A 94.63°C E= 0.95 R7 (CLAMP) B 69.85°C E= 0.95 T1 (WINDING) C 67.62°C E= 0.95 T1 (FERRITE) D 97.50°C E= 0.95 D2 E 76.15°C E= 0.95 D10 F 69.29°C E= 0.95 D12
AN2242 7 Part List
23/31
7 Part List
Table 7. Part List
DesPart Type/
Part ValueDescription Supplier
C10 470uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C11 100uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C12 100N - 50V CERCAP - GENERAL PURPOSE AVX
C14 100N - 50V CERCAP - GENERAL PURPOSE AVX
C15 100N - 50V CERCAP - GENERAL PURPOSE AVX
C16 100N - 50V CERCAP - GENERAL PURPOSE AVX
C17 100N - 50V CERCAP - GENERAL PURPOSE AVX
C18 220N-X2 X2 FILM CAPACITOR - R46-KI 3220 00 L2M ARCOTRONICS
C19 47uF-50V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C20 82uF-400V SMH400VN82xx22A - ALUMINIUM ELCAP - SMH SERIES - 85°C
NIPPON CHEMICON
C21 10N-400V R66MD2100AA6-K - METALLIZED POLYESTER FILM CAP.
ARCOTRONICS
C22 1000uF-16V YXF
ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C23 1000uF-16V YXF
ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C24 220uF-16V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C27 100uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C28 100uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C29 100uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C30 2N2 - 50V CERCAP - GENERAL PURPOSE AVX
C31 100N - 50V CERCAP - GENERAL PURPOSE AVX
C32 100N - 50V CERCAP - GENERAL PURPOSE AVX
C33 10N - 50V CERCAP - GENERAL PURPOSE AVX
C34 220P - 50V CERCAP - GENERAL PURPOSE AVX
C35 2200uF-16V YXF
ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C36 470P - 50V CERCAP - GENERAL PURPOSE AVX
C37 3N3 - 50V CERCAP - GENERAL PURPOSE AVX
C38 100N - 50V CERCAP - GENERAL PURPOSE AVX
C39 100N - 50V CERCAP - GENERAL PURPOSE AVX
C40 10uF-50V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
7 Part List AN2242
24/31
C41 10uF-50V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
C5 DE1E3KX222M 2N2 - Y1 SAFETY CAP. MURATA
C7 1N0 - 200V 200V CERCAP - GENERAL PURPOSE KEMET
C9 470uF-25V YXF ALUMINIUM ELCAP - YXF SERIES - 105°C RUBYCON
D1 2W06G SINGLE PHASE BRIDGE RECTIFIER VISHAY
D10 STPS10L60FP POWER SCHOTTKY RECTIFIER STMicroelectronics
D12 1N5821 LOW DROP POWER SCHOTTKY RECTIFIER STMicroelectronics
D13 LL4148 FAST SWITCHING DIODE VISHAY
D16 LL4148 FAST SWITCHING DIODE VISHAY
D2 STPS8H100FP HIGH VOLTAGE POWER SCHOTTKY RECTIFIER STMicroelectronics
D5 BAV103 FAST SWITCHING DIODE VISHAY
D6 BAV103 FAST SWITCHING DIODE VISHAY
D7 STTH1L06U ULTRAFAST HIGH VOLTAGE RECTIFIER STMicroelectronics
D9 STPS1L60A LOW DROP POWER SCHOTTKY RECTIFIER STMicroelectronics
F1 FUSE T2A FUSE 2 AMP. TIME DELAY WICKMANN
J1 MKDS 1,5/ 2-5,08
PCB TERM. BLOCK, SCREW CONN., PITCH 5MM - 2 WAYS
PHOENIX CONTACT
J2 MPT 0,5/ 8-2,54 PCB TERM. BLOCK, SCREW CONN., PITCH 5MM - 8 WAYS
PHOENIX CONTACT
L1 HF2430-203Y1R0-T01
COMMON MODE CHOKE COIL TDK
L2 2u7-ELC08D POWER INDUCTOR PANASONIC
L3 2u7-ELC08D POWER INDUCTOR PANASONIC
L4 22uH-RCH654 POWER INDUCTOR SUMIDA
L5 2u7-ELC08D POWER INDUCTOR PANASONIC
Q1 STP4NK60ZFP N-CHANNEL POWER MOSFET STMicroelectronics
Q2 BC847B SMALL SIGNAL NPN TRANSISTORS STMicroelectronics
Q3 BC847B SMALL SIGNAL NPN TRANSISTORS STMicroelectronics
Q4 BC847B SMALL SIGNAL NPN TRANSISTORS STMicroelectronics
Q5 BC847B SMALL SIGNAL NPN TRANSISTORS STMicroelectronics
R1 NTC_10R S236 NTC RESISTOR P/N B57236S0100M000 EPCOS
R10 10K SMD STANDARD FILM RES - 1/8W - 1% - 100ppm/°C BC COMPONENTS
R12 10K SMD STANDARD FILM RES - 1/8W - 1% - 100ppm/°C BC COMPONENTS
R13 36K SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R14 30K SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
Table 7. Part List
DesPart Type/
Part ValueDescription Supplier
AN2242 7 Part List
25/31
R15 6K2 SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R16 1K0 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R17 82R SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R18 0R47 SFR25 AXIAL STANDARD FILM RES - 0.4W - 5% - 250ppm/°C
BC COMPONENTS
R19 0R47 SFR25 AXIAL STANDARD FILM RES - 0.4W - 5% - 250ppm/°C
BC COMPONENTS
R2 3R9 PR01 AXIAL STANDARD FILM RES - 1W - 5% - 250ppm/°C
BC COMPONENTS
R20 1K8 SMD STANDARD FILM RES - 1/4W - 1% - 100ppm/°C BC COMPONENTS
R21 3K9 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R22 27K SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R23 1K0 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R24 1K0 SMD STANDARD FILM RES - 1/4W - 1% - 100ppm/°C BC COMPONENTS
R25 3K3 SMD STANDARD FILM RES - 1/8W - 1% - 100ppm/°C BC COMPONENTS
R26 1K0 SMD STANDARD FILM RES - 1/8W - 1% - 100ppm/°C BC COMPONENTS
R27 5K6 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R28 1K0 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R29 10K SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R30 270R SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R32 1K0 SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R33 1K0 SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R34 1K0 SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R35 1K0 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R36 3K3 SMD STANDARD FILM RES - 1/8W - 5% - 250ppm/°C BC COMPONENTS
R4 4K7 SFR25 AXIAL STANDARD FILM RES - 0.4W - 5% - 250ppm/°C
BC COMPONENTS
R5 470K SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R6 330K SMD STANDARD FILM RES - 1/4W - 5% - 250ppm/°C BC COMPONENTS
R7 33K-2W PR02 AXIAL STANDARD FILM RES - 2W - 5% - 250ppm/°C
BC COMPONENTS
R8 33R PR02 AXIAL STANDARD FILM RES - 2W - 5% - 250ppm/°C
BC COMPONENTS
T1 SRW28LEC-E01 H117
POWER TRANSFORMER TDK
U2 L6668 PRIMARY CONTROLLER STMicroelectronics
Table 7. Part List
DesPart Type/
Part ValueDescription Supplier
7 Part List AN2242
26/31
U3 SFH617A-4 OPTOCOUPLER INFINEON
U4 TS2431ILT PROGRAMMABLE SHUNT VOLTAGE REFERENCE STMicroelectronics
HS1 LS220 Q1 HEAT SINK ABL ALUMINIUM COMP.
HS2 507302 D2 HEAT SINK AAVID THERMALLOY
HS3 507302 D10 HEAT SINK AAVID THERMALLOY
Table 7. Part List
DesPart Type/
Part ValueDescription Supplier
AN2242 8 PCB Layout
27/31
8 PCB Layout
Figure 29. Silk Screen -Top Side
Figure 30. Silk Screen -Bottom Side
Figure 31. Copper Tracks
9 Transformer Specification AN2242
28/31
9 Transformer Specification
APPLICATION TYPE: Consumer, Home Appliance
TRANSFORMER TYPE: Open
WINDING TYPE: Layer
COIL FORMER: Horizontal type, 6+6 pins
MAX. TEMP. RISE: 45°C
MAX. OPERATING AMBIENT TEMP.: 60°C
MAINS INSULATION: ACC. WITH EN60065
9.1 Electrical Characteristics
CONVERTER TOPOLOGY: Flyback, CCM/DCM Mode
CORE TYPE: EER28L - PC40 or equivalent
TYPICAL OPERATING FREQ.: 65kHz
PRIMARY INDUCTANCE: 910 µH ±10% at 1kHz - 0.25V (1)
LEAKAGE INDUCTANCE: 15 µH MAX at 100kHz - 0.25V (2)
MAX. PEAK PRIMARY CURRENT: 1.65 Apk
RMS PRIMARY CURRENT: 0.65 ARMS
Note: 1 Measured between pins 1-3
2 Measured between pins 1-3 with all secondary windings shorted
Figure 32. "Transformer Electrical Diagram
1
3
PRIM
5
6
AUX
+1.8
7
+3.3
10
9
11
+5V
12
+12V
8
AN2242 9 Transformer Specification
29/31
Table 8. Winding Characteristics
Figure 33. Winding Position
Note: Primaries A & B are in parallel
9.2 Mechanical Aspect
MAXIMUM HEIGHT FROM PCB: 30mm
COIL FORMER TYPE:HORIZONTAL, 6+6 PINS (PINS #2 and #4 ARE REMOVED)
PIN DISTANCE: 5mm
ROW DISTANCE: 30 mm
PINS #3 and #4 ARE REMOVED
EXTERNAL COPPER SHIELD: 12mm WIDTH
9.3 Manufacturer
TDK Electronics Europe - Germany
Transformer P/N: SRW28LEC-E01H117
PINS WINDINGO/P RMS
CURRENTNUMBER OF
TURNSWIRE TYPE
3-1 PRIMARY - A 0.32 ARMS 95 G2 - 2X Φ 0.23mm
12-11 12V 2.3 ARMS 9 G2 - 3X Φ 0.45mm
11-10 5V 3 ARMS 7 SPACED G2 - 3X Φ 0.45mm
9-8 3.3V 0.6 ARMS 2 G2 - 3X Φ 0.45mm
8-7 1.8V 2.1 ARMS 3 G2 - 3X Φ 0.45mm
3-1 PRIMARY 0.32 ARMS 95 G2 - 2X Φ 0.23mm
5-6 AUX 0.05 ARMS 17 SPACED G2 - Φ 0.23mm
COIL FORMER
INSULATING TAPE1.8V – 3.3V
5V12V
PRIMARY - A
PRIMARY - BAUX
44 44
10 Revision History AN2242
30/31
10 Revision History
Date Revision Changes
05-Dec-2005 1.0 First edition
AN2242 10 Revision History
31/31
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