Class 2: The Fundamentals of Designing with Semiconductors

The World Leader in High Performance Signal Processing Solutions

THE FUNDAMENTALS OF DESIGNING WITH SEMICONDUCTORS FOR SIGNAL

PROCESSING APPLICATIONS

Class 2 - THE OP AMP

Presented by David Kress

Analog to Electronic signal processing

Sensor(INPUT)

Digital ProcessorAmp Converter

Actuator(OUTPUT)

Amp Converter

Analog to Electronic signal processing

Sensor(INPUT)

Digital ProcessorAmp Converter

Actuator(OUTPUT)

Amp Converter

Amplifiers and Operational AmplifiersAmplifiers

Make a low-level, high-source impedance signal into a high-level, low-source impedance signal

Op amps, power amps, RF amps, instrumentation amps, etc.Most complex amplifiers built up from combinations of op

ampsOperational amplifiers

Three-terminal device (plus power supplies)Amplify a small signal at the input terminals to a very, very

large one at the output terminal

Operational Amplifiers

OperationalOp amps can be configured with feedback networks in multiple

ways to perform ‘operations’ on input signals‘Operations’ include positive or negative gain, filtering, nonlinear

transfer functions, comparison, summation, subtraction, reference buffering, differential amplification, integration, differentiation, etc.

ApplicationsFundamental building block for analog designSensor input amplifierSimple and complex filters – anti-aliasingADC driver

Original vacuum-tube op-amp from Philbrick Research in 1953 – it used +/- 300V supplies

0.1 in

(ALL PACKAGES ABOVE TO SAME SCALE)

8-SOICmSOIC

MSOP8SOT-23SC-70 14-SOIC

SOT-23SC-70

THE RELATIVE SCALE OF SOME MODERN IC OP AMP PACKAGES

AD823 JFET Input Op Amp Simplified Schematic

INPUTS

+VS

-VS

Q57A=19

Q44A=1

Q43

Q58

Q62

R44

S1NS1P

VB

Q49Q61Q72J6J1

Q48

Q35Q53

I1 Q56

Q59A=1

Q17A=19

OUTPUTQ60

R28

(-)

(+)

VBE + 0.3V

BIAS CURRENT = 25pA MAX @ +25°CINPUT OFFSET VOLTAGE = 0.8mV MAX @ +25°CINPUT VOLTAGE NOISE = 15nV/HzINPUT CURRENT NOISE = 1fA/Hz

1-9

Standard op amp symbol

INPUTS

(+)

(-)

INPUTS

(+)

(-)

The Ideal Op Amp and its Attributes

OP AMP

OP AMP INPUTS:

OP AMP OUTPUT:

High Input Impedance Low Bias Current Respond to Differential Mode Voltages Ignore Common Mode Voltages

Low Source Impedance

IDEAL OP AMP ATTRIBUTES: Infinite Differential Gain Zero Common Mode Gain Zero Offset Voltage Zero Bias Current

OUTPUT

POSITIVE SUPPLY

NEGATIVE SUPPLY

INPUTS

(+)

(-)

Operational Amplifier Circuit Design

Use of negative feedbackThe output signal, or a controlled portion of it, is fed back to the

negative (-) input terminalThe op amp will adjust the output signal until the input difference

goes to zeroExample of high-gain

Assume op amp gain of 106 (one million)Apply signal of one volt to positive inputFeedback directly from output to negative inputOutput will go to one volt (minus one microvolt)Difference at input will be on microvolt

Key Op Amp Performance Features

Bandwidth and slew rateThe speed of the op ampBandwidth is the highest operating frequency of the op ampSlew rate is the maximum rate of change of the outputDetermined by the frequency of the signal and the gain needed

Offset voltage and currentThe errors of the op ampDetermines measurement accuracy

NoiseOp amp noise limits how small a signal can be amplified with good

fidelity

1-13

Non-inverting Mode Op Amp Stage

VINVOUT

OP AMP

RF

RG

G = VOUT/VIN

= 1 + (RF/RG)

1-14

Inverting Mode Op Amp Stage

VIN

= - RF/RG

VOUT

OP AMP

RFRG

G = VOUT/VIN

SUMMING POINT

1-15

Non-Inverting Amplifier gain

RFB

R IN

G =OUT

V IN

V

= 1+RFB

R IN

G =OUT

V IN

V

= 1+RFB

R IN

G =OUT

V IN

V

= 1+VIN

VOUT

RFB

RIN

IVIN

VOUT

RFB

RIN

I

Single Pole Op Amp Active Filters

(A)LOWPASS

(B)HIGHPASS

+

-+

-

5-38

1-17

Open Loop Gain (Bode Plot)

OPENLOOPGAINdB

OPENLOOPGAINdB

6dB/OCTAVE6dB/OCTAVE

12dB/OCTAVE

OPENLOOPGAINdB

OPENLOOPGAINdB

6dB/OCTAVE6dB/OCTAVE

12dB/OCTAVE

1-18

Gain-Bandwidth Product

GAINdB OPEN LOOP GAIN, A(s)

IF GAIN BANDWIDTH PRODUCT = XTHEN Y · fCL = X

fCL =XY

WHERE fCL = CLOSED-LOOPBANDWIDTH

LOG ffCL

NOISE GAIN = Y

Y = 1 +R2

R1

GAINdB OPEN LOOP GAIN, A(s)

IF GAIN BANDWIDTH PRODUCT = XTHEN Y · fCL = X

fCL =XY

WHERE fCL = CLOSED-LOOPBANDWIDTH

LOG ffCL

NOISE GAIN = Y

Y = 1 +R2

R1

1-19

Noise Gain

+

-

IN +

-

+

-

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2

R1 R3

Voltage Noise and Offset Voltage of the op amp are reflected to the output by the Noise Gain.

Noise Gain, not Signal Gain, is relevant in assessing stability.

Circuit C has unchanged Signal Gain, but higher Noise Gain, thusbetter stability, worse noise, and higher output offset voltage.

IN

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = R2/R1

Noise Gain = 1 + R2/R1

Signal Gain =

Noise Gain = 1 + R2

+

-

IN +

-

+

-

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2

R1 R3

IN

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = R2/R1

Noise Gain = 1 + R2/R1

Signal Gain =

Noise Gain = 1 + R2

+

-

IN +

-

+

-

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2

R1 R3

Voltage Noise and Offset Voltage of the op amp are reflected to the output by the Noise Gain.

Noise Gain, not Signal Gain, is relevant in assessing stability.

Circuit C has unchanged Signal Gain, but higher Noise Gain, thusbetter stability, worse noise, and higher output offset voltage.

IN

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = R2/R1

Noise Gain = 1 + R2/R1

Signal Gain =

Noise Gain = 1 + R2

+

-

IN +

-

+

-

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = - R2/R1

Noise Gain = 1 + R2

R1 R3

IN

A B C

R1

R2 IN

R1

R2R2

R1

IN

Signal Gain = 1 + R2/R1

Noise Gain = 1 + R2/R1

Signal Gain = R2/R1

Noise Gain = 1 + R2/R1

Signal Gain =

Noise Gain = 1 + R2

1-20

AD847 Open Loop Gain

1-21

AD8051 Phase Margin

1-22

VFB and CFB Amplifiers

~

+

–

v–A(s) v

A(s) = OPEN LOOP GAINVOUT = A(s)*v

R2

R1

VIN +

–i

–T(s) i

T(s)

RO

i×1

R2R1

VIN

VOUT×1

T(s) = TRANSIMPEDANCE OPEN LOOP GAINVOUT = -T(s)*i

VOUT~

+

–

v–A(s) v

A(s) = OPEN LOOP GAINVOUT = A(s)*v

R2

R1

VIN +

–i

–T(s) i

T(s)

RO

i×1

R2R1

VIN

VOUT×1

T(s) = TRANSIMPEDANCE OPEN LOOP GAINVOUT = -T(s)*i

VOUT

1-23

Current Feedback Amplifier Frequency Response

Feedback resistor fixed for optimum performance. Larger values reduce bandwidth, smaller values may cause instability.

For fixed feedback resistor, changing gain has little effect on bandwidth.

Current feedback op amps do not have a fixed gain-bandwidth product.

GAINdB G1

G2

G1 · f1 G2 · f2

f1 f2 LOG f

Feedback resistor fixed for optimum performance. Larger values reduce bandwidth, smaller values may cause instability.

For fixed feedback resistor, changing gain has little effect on bandwidth.

Current feedback op amps do not have a fixed gain-bandwidth product.

GAINdB G1

G2

G1 · f1 G2 · f2

f1 f2 LOG f

GAINdB G1

G2

G1 · f1 G2 · f2

f1 f2 LOG f

1-24

Standard Input Stage (Differential Pair)

VINVIN

1-25

PNP Input Stage

+VS

-VS

+VS

-VS

1-26

Compound Input Stage

+VS

-VS

+VS

-VS

1-27

Output Stages. Emitter Follower for Standard Configuration And Common Emitter for “Rail-to-Rail” Configuration

+VS

EMITTER FOLLOWER COMMON EMITTER

+VS

-VS -VS

OUTPUT OUTPUT

INPUT OFFSET VOLTAGE

Offset Voltage: The differential voltage which must be applied to the input of an op amp to produce zero output.

Ranges: Chopper Stabilized Op Amps: <1µV General Purpose Precision Op Amps: 50-500µV Best Bipolar Op Amps: 10-25µV Best FET Op Amps: 100-1,000µV High Speed Op Amps: 100-2,000µV Untrimmed CMOS Op Amps: 5,000-50,000µV DigiTrim™ CMOS Op Amps: <1,000µV

-

+

VOS

1-29

Offset Adjustment Pins

-

+

2

3

1

87

4

6

+VS OR -VS +VS

-VS

-

+

2

3

1

87

4

6

+VS OR -VS +VS

-VS

1-30

External Offset Adjustment

VOUT = – R2R1

VIN ± R2R3

VR

MAXOFFSET

VOUT = – R2R1

VIN ± 1 + R2R1

RPRP + R3

VR

MAXOFFSET

RP = R1||R2 IF IB+ IB-

RP 50 IF IB+ IB-

–

+

(A)

VIN

VOUT

R1

R2

R3

+VR–VR

RA RB

NOISE GAIN =

R2R1||(R3 + RA||RB)

1 +

–

+

(B)

VIN

VOUT

R1

R2

R3RP

+VR–VR

RBRA

NOISE GAIN =R2R1

1 +

VOUT = – R2R1

VIN ± R2R3

VR

MAXOFFSET

VOUT = – R2R1

VIN ± R2R3

VR

MAXOFFSET

VOUT = – R2R1

VIN ± 1 + R2R1

RPRP + R3

VR

MAXOFFSET

RP = R1||R2 IF IB+ IB-

RP 50 IF IB+ IB-

VOUT = – R2R1

VIN ± 1 + R2R1

RPRP + R3

RPRP + R3

VR

MAXOFFSET

RP = R1||R2 IF IB+ IB-

RP 50 IF IB+ IB-

–

+

(A)

VIN

VOUT

R1

R2

R3

+VR–VR

RA RB

NOISE GAIN =

R2R1||(R3 + RA||RB)

1 +

–

+

(A)

VIN

VOUT

R1

R2

R3

+VR–VR

RA RB

NOISE GAIN =

R2R1||(R3 + RA||RB)

1 +

–

+

(B)

VIN

VOUT

R1

R2

R3RP

+VR–VR

RBRA

NOISE GAIN =R2R1

1 +

–

+

(B)

VIN

VOUT

R1

R2

R3RP

+VR–VR

RBRA

NOISE GAIN =R2R1

1 +

1-31

Input Bias Current

+IB+

IB-

+IB+

IB-

+IB+

IB-

+IB+

IB-

1-32

Bias Current Compensation

–

+

VO

R1

R2

R3 = R1 || R2

IB–

IB+

VO = R2 (IB– – IB+)

= R2 IOS

= 0, IF IB+ = IB–

NEGLECTING VOS

–

+

VO

R1

R2

R3 = R1 || R2

IB–

IB+

–

+

VO

R1

R2

R3 = R1 || R2

IB–

IB+

VO = R2 (IB– – IB+)

= R2 IOS

= 0, IF IB+ = IB–

NEGLECTING VOS

1-33

Total Offset Voltage Calculations

OFFSET (RTO) = VOS 1 + R2R1 + IB+• R3

R2R11 + – IB–• R2

OFFSET (RTI ) = VOS + IB+• R3 – IB–R1•R2

R1 + R2

FOR BIAS CURRENT CANCELLATION:

OFFSET (RTI) = VOS IF IB+ = IB– AND R3 = R1•R2

R1 + R2

NOISE GAIN =

1 + R2

R1NG =

GAIN FROM "A" TO OUTPUT

=

GAIN FROM"B" TO OUTPUT

= –R2

R1

–

+

VOS

R2R1

R3

IB–

IB+

VOUTA

B

–

+

VOS

R2R1

R3

IB–

IB+

VOUTA

B

OFFSET (RTO) = VOS 1 + R2R1 + IB+• R3

R2R11 + – IB–• R2 OFFSET (RTO) = VOS 1 + R2

R1 + IB+• R3R2R11 + – IB–• R2

OFFSET (RTI ) = VOS + IB+• R3 – IB–R1•R2

R1 + R2 OFFSET (RTI ) = VOS + IB+• R3 – IB–

R1•R2R1 + R2

FOR BIAS CURRENT CANCELLATION:

OFFSET (RTI) = VOS IF IB+ = IB– AND R3 = R1•R2

R1 + R2

FOR BIAS CURRENT CANCELLATION:

OFFSET (RTI) = VOS IF IB+ = IB– AND R3 = R1•R2

R1 + R2

NOISE GAIN =

1 + R2

R1NG =

GAIN FROM "A" TO OUTPUT

=

NOISE GAIN =

1 + R2

R1NG =

GAIN FROM "A" TO OUTPUT

=

GAIN FROM"B" TO OUTPUT

= –R2

R1GAIN FROM

"B" TO OUTPUT= –

R2

R1

–

+

VOS

R2R1

R3

IB–

IB+

VOUTA

B

–

+

VOS

R2R1

R3

IB–

IB+

VOUTA

B

1-34

Input Impedance

IB+ IB–

Zdiff

Zcm+Zcm–

– INPUT+ INPUT

IB+ IB–

Zdiff

Zcm+Zcm–

– INPUT+ INPUT

1-35

Current Feedback Input Resistance

X1

Z+

+INPUT - INPUT

Z-

X1

Z+

+INPUT - INPUT

Z-

1-36

Voltage Noise

VN

–

+

VN

–

+

VN

–

+

VN

–

+

VN

–

+

VN

–

+

VN

–

+

1-37

Equivalent Noise Bandwidth

GAUSSIANNOISE

SOURCE

GAUSSIANNOISE

SOURCE

SINGLE POLELOWPASSFILTER, fC

BRICK WALLLOWPASS

FILTER, 1.57fC

IDENTICAL LEVELSSAME

RMS NOISELEVEL

EQUIVALENT NOISE BANDWIDTH = 1.57 fC

GAUSSIANNOISE

SOURCE

GAUSSIANNOISE

SOURCE

SINGLE POLELOWPASSFILTER, fC

BRICK WALLLOWPASS

FILTER, 1.57fC

IDENTICAL LEVELSSAME

RMS NOISELEVEL

EQUIVALENT NOISE BANDWIDTH = 1.57 fC

1-38

Current Noise

IN–

-

+IN+

IN–

-

+IN+

IN–

-

+IN+

IN–

-

+IN+

1-39

Total Noise Calculation

FCL = CLOSED LOOP BANDWIDTH

R1

VON

Rp

In-

In+

R2

Vn

VR2J

VR1J

VRPJ

+

= BW [(In-2)R22] [NG] + [(In+2)RP

2] [NG] + VN2 [NG] + 4kTR2 [NG-1] + 4kTR1 [NG-1] + 4kTRP [NG]VON

BW = 1.57 FCL

FCL = CLOSED LOOP BANDWIDTH

R1

VON

Rp

In-

In+

R2

Vn

VR2J

VR1J

VRPJ

+

R1

VON

Rp

In-

In+

R2

Vn

VR2J

VR1J

VRPJ

+

= BW [(In-2)R22] [NG] + [(In+2)RP

2] [NG] + VN2 [NG] + 4kTR2 [NG-1] + 4kTR1 [NG-1] + 4kTRP [NG]VON = BW [(In-2)R2

2] [NG] + [(In+2)RP2] [NG] + VN

2 [NG] + 4kTR2 [NG-1] + 4kTR1 [NG-1] + 4kTRP [NG]VON

BW = 1.57 FCL

1-40

Dominant Noise Source Determined by Input Impedance

CONTRIBUTIONFROM

AMPLIFIERVOLTAGE NOISE

AMPLIFIERCURRENT NOISE

FLOWING IN R

JOHNSONNOISE OF R

VALUES OF R

0 3k 300k

3 3 3

0

0

3

7

300

70

RTI NOISE (nV / Hz)

Dominant Noise Source is Highlighted

R

+

–

EXAMPLE: OP27Voltage Noise = 3nV / HzCurrent Noise = 1pA / HzT = 25°C

OP27

R2R1

Neglect R1 and R2Noise Contribution

CONTRIBUTIONFROM

AMPLIFIERVOLTAGE NOISE

AMPLIFIERCURRENT NOISE

FLOWING IN R

JOHNSONNOISE OF R

VALUES OF R

0 3k 300k

3 3 3

0

0

3

7

300

70

RTI NOISE (nV / Hz)

Dominant Noise Source is Highlighted

R

+

–

EXAMPLE: OP27Voltage Noise = 3nV / HzCurrent Noise = 1pA / HzT = 25°C

OP27

R2R1

Neglect R1 and R2Noise Contribution

1-41

1/f Noise Bandwidth

1/f Corner Frequency is a figure of merit for op amp noise performance (the lower the better)

Typical Ranges: 2Hz to 2kHz

Voltage Noise and Current Noise do not necessarily have the same 1/f corner frequency

3dB/Octave

WHITE NOISE

LOG f

CORNER1f

NOISEnV / Hz

orHz

en, in

k

FC

k FC1f

en, in =3dB/Octave

WHITE NOISE

LOG f

CORNER1f

NOISEnV / Hz

orpA / Hz

en, in

k

FC

k FC1f

en, in =

1/f Corner Frequency is a figure of merit for op amp noise performance (the lower the better)

Typical Ranges: 2Hz to 2kHz

Voltage Noise and Current Noise do not necessarily have the same 1/f corner frequency

3dB/Octave

WHITE NOISE

LOG f

CORNER1f

NOISEnV / Hz

orHz

en, in

k

FC

k FC1f

en, in =3dB/Octave

WHITE NOISE

LOG f

CORNER1f

NOISEnV / Hz

orpA / Hz

en, in

k

FC

k FC1f

en, in =

1-42

RMS to Peak to Peak Voltage Comparison Chart

1-43

The Peak-to-Peak Noise in the 0.1 Hz. to 10 Hz. Bandwidth

1-44

Resistor Noise

V NR R V NR R

ALL resistors have a voltage noise of V NR = 4kTBR)

T = Absolute Temperature = T ( ° C) + 273.15

B = Bandwidth (Hz)

k = Boltzmann ’ s Constant (1.38 x 10 - 23 J/K)

A 1000 resistor generates 4 nV / Hz @ 25 ° C

V NR R V NR R

ALL resistors have a voltage noise of V = 4kTBR)

° C) + 273.15

B = Bandwidth (Hz)

k = Boltzmann ’ s - 23 J/K)

A 1000 Hz @ 25 ° C

1-45

THD & THD+N Definitions

Vs = Signal Amplitude (RMS Volts)

V2 = Second Harmonic Amplitude (RMS Volts)

Vn = nth Harmonic Amplitude (RMS Volts)

Vnoise = RMS value of noise over measurement bandwidth

THD + N =

THD =

Vs

Vs

V22 + V3

2 + V42 + . . . + Vn

2 + Vnoise2

V22 + V3

2 + V42 + . . . + Vn

2

1-46

Slew Rate

10%

90%FINAL VALUE

OVERSHOOT

RINGING

VO

LT

AG

E

TIME

10%

OVERSHOOT

RINGING

10%

SLEW RATE =

OVERSHOOT

RINGING

VO

LT

AG

E

TIME

V

T

VT

10%

90%FINAL VALUE

OVERSHOOT

RINGING

VO

LT

AG

E

TIME

10%

OVERSHOOT

RINGING

10%

SLEW RATE =

OVERSHOOT

RINGING

VO

LT

AG

E

TIME

V

T

VT

1-47

Slew Rate and Full Power Bandwidth

Slew Rate = Maximum rate at which the output voltage of

Ranges: A few volts / s to several thousand volts / s

For a sinewave, Vout = Vpsin2 f t

If 2 V p = full output span of op amp, then

an op amp can change

dV/dt = 2π f Vp cos 2π f t

(dV/dt)max = 2fVp

Slew Rate = (dV/dt)max = 2 * FPBW * Vp

FPBW = Slew Rate / 2Vp

Slew Rate = Maximum rate at which the output voltage of

Ranges: A few volts / s to several thousand volts / s

For a sinewave, Vout = Vpsin2 f t

If 2 V pIf 2 V p = full output span of op amp, then

an op amp can change

dV/dt = 2π f Vp cos 2π f t

(dV/dt)max = 2fVp

Slew Rate = (dV/dt)max = 2 * FPBW * Vp

FPBW = Slew Rate / 2Vp

1-48

Settling Time

OUTPUT

ERROR

BAND

FINAL

SETTLING

RECOVERY

TIME

SLEW

TIME

DEAD

TIME

SETTLING TIME

OUTPUT

ERROR

BAND

FINAL

SETTLING

RECOVERY

TIME

SLEW

TIME

DEAD

TIME

SETTLING TIME

Error band is usually defined to be a percentage of the step 0.1%0.05%, 0.01%, etc.

Settling time is non-linear; it may take 30 times as long to settle to0.01% as to 0.1%.

Manufacturers often choose an error band which makes the op amp look good.

1-49

Common Mode Rejection Ratiofor the OP177

160

140

120

100

80

60

40

20

0

CMRdB

FREQUENCY - Hz

CMR =20 log10 CMRR

0.01 0.1 1 10 100 1k 10k 100k 1M

160

140

120

100

80

60

40

20

0

CMRdB

FREQUENCY - Hz

CMR =20 log10 CMRR

0.01 0.1 1 10 100 1k 10k 100k 1M

1-50

Power Supply Rejection Ratio

0.01 0.1 1 10 100 1k 10k 100k 1M

160

140

120

100

80

60

40

20

0

PSRdB

FREQUENCY - Hz

PSR =20 log10 PSRR

0.01 0.1 1 10 100 1k 10k 100k 1M

160

140

120

100

80

60

40

20

0

PSRdB

FREQUENCY - Hz

PSR =20 log10 PSRR

1-51

Maximum Power Chart (from the AD8001)

1-52

Input Protection

+VS

-VS

RS

+

-

+VS

-VS

RS

+

-

1-53

Typical Absolute Maximum Ratings

Single-Supply Op Amps Single Supply Offers:

Lower Power Battery Operated Portable Equipment Requires Only One Voltage

Design Tradeoffs: Reduced Signal Swing Increases Sensitivity to Errors

Caused by Offset Voltage, Bias Current, Finite Open-

Loop Gain, Noise, etc. Must Usually Share Noisy Digital Supply Rail-to-Rail Input and Output Needed to Increase Signal

Swing Precision Less than the best Dual Supply Op Amps

but not Required for All Applications Many Op Amps Specified for Single Supply, but do not

have Rail-to-Rail Inputs or Outputs

1-55

Next webcasts

Challenges in Embedded Design for Motor Control systemsMarch 16th at Noon (ET)

MEMs solutions for Instrumentation applicationsApril 13th at Noon (EDT)

Multi-parameter Vital Signs Patient MonitorsMay 18th at Noon (EDT)

www.analog.com/webcast

Fundamentals Webcasts 2011

January Introduction and Fundamentals of Sensors February The Op Amp March Beyond the Op Amp April Converters, Part 1, Understanding Sampled Data Systems May Converters, Part 2, Digital-to-Analog Converters June Converters, Part 3, Analog-to-Digital Converters July Powering your circuit August RF: Making your circuit mobile September Fundamentals of DSP/Embedded System design October Challenges in Industrial Design November Tips and Tricks for laying out your PC board December Final Exam, Ask Analog Devices

www.analog.com/webcast

The World Leader in High Performance Signal Processing Solutions

Thank You