Multi Level Topologies Survey

724 IEEE TRANSACTIONS ON INDUSTRIAL ELECTRONICS, VOL. 49, NO. 4, AUGUST 2002

Multilevel Inverters: A Survey of Topologies,Controls, and Applications

José Rodríguez, Senior Member, IEEE, Jih-Sheng Lai, Senior Member, IEEE, andFang Zheng Peng, Senior Member, IEEE

Abstract—Multilevel inverter technology has emerged re-cently as a very important alternative in the area of high-powermedium-voltage energy control. This paper presents the mostimportant topologies like diode-clamped inverter (neutral-pointclamped), capacitor-clamped (flying capacitor), and cascadedmulticell with separate dc sources. Emerging topologies likeasymmetric hybrid cells and soft-switched multilevel inverters arealso discussed. This paper also presents the most relevant controland modulation methods developed for this family of converters:multilevel sinusoidal pulsewidth modulation, multilevel selectiveharmonic elimination, and space-vector modulation. Specialattention is dedicated to the latest and more relevant applicationsof these converters such as laminators, conveyor belts, and unifiedpower-flow controllers. The need of an active front end at theinput side for those inverters supplying regenerative loads is alsodiscussed, and the circuit topology options are also presented.Finally, the peripherally developing areas such as high-voltagehigh-power devices and optical sensors and other opportunitiesfor future development are addressed.

Index Terms—Medium-voltage drives, multilevel converter,multilevel inverter, power converters.

I. INTRODUCTION

I N RECENT YEARS, industry has begun to demand higherpower equipment, which now reaches the megawatt level.

Controlled ac drives in the megawatt range are usually con-nected to the medium-voltage network. Today, it is hard to con-nect a single power semiconductor switch directly to medium-voltage grids (2.3, 3.3, 4.16, or 6.9 kV). For these reasons, anew family of multilevel inverters has emerged as the solutionfor working with higher voltage levels [1]–[3].

Multilevel inverters include an array of power semicon-ductors and capacitor voltage sources, the output of whichgenerate voltages with stepped waveforms. The commutationof the switches permits the addition of the capacitor voltages,which reach high voltage at the output, while the powersemiconductors must withstand only reduced voltages. Fig. 1shows a schematic diagram of one phase leg of inverters withdifferent numbers of levels, for which the action of the power

Manuscript received December 2002 ; revised April 2002. Abstract publishedon the Internet May 16, 2002. This work was supported by the Chilean ResearchFund CONICYT under Grant 1990837, Grant 1010096, and Grant 7010096 andby the University Federico Santa María.

J. Rodríguez is with the Departamento de Electronica, Universidad TécnicaFederico Santa María, Valparaiso, Chile (e-mail: [email protected]).

J.-S. Lai is with Virginia Polytechnic Institute and State University, Blacks-burg, VA 24061-0111 USA.

F. Z. Peng is with the Department of Electrical and Computer Engineering,Michigan State University, East Lansing, MI 48826-1226 USA.

Publisher Item Identifier 10.1109/TIE.2002.801052.

Fig. 1. One phase leg of an inverter with (a) two levels, (b) three levels, and(c) n levels.

semiconductors is represented by an ideal switch with severalpositions. A two-level inverter generates an output voltagewith two values (levels) with respect to the negative terminalof the capacitor [see Fig. 1(a)], while the three-level invertergenerates three voltages, and so on.

Considering that is the number of steps of the phase voltagewith respect to the negative terminal of the inverter, then thenumber of steps in the voltage between two phases of the load

is

(1)

and the number of stepsin the phase voltage of a three-phaseload in wye connection is

(2)

The term multilevel starts with the three-level inverter intro-duced by Nabaeet al. [4]. By increasing the number of levelsin the inverter, the output voltages have more steps generatinga staircase waveform, which has a reduced harmonic distortion.However, a high number of levels increases the control com-plexity and introduces voltage imbalance problems.

Three different topologies have been proposed for multilevelinverters: diode-clamped (neutral-clamped) [4]; capac-itor-clamped (flying capacitors) [1], [5], [6]; and cascadedmulticell with separate dc sources [1], [7]–[9]. In addition, sev-eral modulation and control strategies have been developed oradopted for multilevel inverters including the following: mul-tilevel sinusoidal pulsewidth modulation (PWM), multilevelselective harmonic elimination, and space-vector modulation(SVM).

The most attractive features of multilevel inverters are as fol-lows.

1) They can generate output voltages with extremely lowdistortion and lower .

0278-0046/02$17.00 © 2002 IEEE

RODRÍGUEZet al.: MULTILEVEL INVERTERS 725

2) They draw input current with very low distortion.3) They generate smaller common-mode (CM) voltage, thus

reducing the stress in the motor bearings. In addition,using sophisticated modulation methods, CM voltagescan be eliminated [8].

4) They can operate with a lower switching frequency.

The results of a patent search show that multilevel invertercircuits have been around for more than 25 years. An earlytraceable patent appeared in 1975 [9], in which the cascadeinverter was first defined with a format that connects separatelydc-sourced full-bridge cells in series to synthesize a staircase acoutput voltage. Through manipulation of the cascade inverter,with diodes blocking the sources, the diode-clamped multilevelinverter was then derived [10]. The diode-clamped inverterwas also called the neutral-point clamped (NPC) inverterwhen it was first used in a three-level inverter in which themid-voltage level was defined as the neutral point. Becausethe NPC inverter effectively doubles the device voltage levelwithout requiring precise voltage matching, the circuit topologyprevailed in the 1980s. The application of the NPC inverterand its extension to multilevel converter was found in [11].Although the cascade inverter was invented earlier, its applica-tions did not prevail until the mid–1990s. Two major patents[12], [13] were filed to indicate the superiority of cascadeinverters for motor drive and utility applications. Due to thegreat demand of medium-voltage high-power inverters, thecascade inverter has drawn tremendous interest ever since.Several patents were found for the use of cascade inverters inregenerative-type motor drive applications [14]–[16]. The lastentry for U.S. multilevel inverter patents, which were defined asthe capacitor-clamped multilevel inverters, came in the 1990s[17], [18]. Today, multilevel inverters are extensively usedin high-power applications with medium voltage levels. Thefield applications include use in laminators, mills, conveyors,pumps, fans, blowers, compressors, and so on.

This paper presents state-of-the-art multilevel technology,considering well-established and emerging topologies as wellas their modulation and control techniques. Special attentionis dedicated to the latest and more relevant industrial applica-tions of these converters. Finally, the possibilities for futuredevelopment are addressed.

II. I NVERTER TOPOLOGIES

A. Diode-Clamped Inverter

A three-level diode-clamped inverter is shown in Fig. 2(a). Inthis circuit, the dc-bus voltage is split into three levels by twoseries-connected bulk capacitors, and . The middle pointof the two capacitorsn can be defined as the neutral point. Theoutput voltage has three states: , 0, and . Forvoltage level , switches and need to be turned on;for , switches and need to be turned on; and forthe 0 level, and need to be turned on.

The key components that distinguish this circuit from aconventional two-level inverter are and . These twodiodes clamp the switch voltage to half the level of the dc-busvoltage. When both and turn on, the voltage acrossaand 0 is , i.e., . In this case, balances out

Fig. 2. Diode-clamped multilevel inverter circuit topologies. (a) Three-level.(b) Five-level.

the voltage sharing between and with blockingthe voltage across and blocking the voltage across

. Notice that output voltage is ac, and is dc. Thedifference between and is the voltage across , whichis . If the output is removed out betweena and 0, thenthe circuit becomes a dc/dc converter, which has three outputvoltage levels: , , and 0.

Fig. 2(b) shows a five-level diode-clamped converter in whichthe dc bus consists of four capacitors,, , , and . Fordc-bus voltage , the voltage across each capacitor is ,and each device voltage stress will be limited to one capacitorvoltage level through clamping diodes.

To explain how the staircase voltage is synthesized, the neu-tral pointn is considered as the output phase voltage referencepoint. There are five switch combinations to synthesize five levelvoltages acrossa andn.

1) For voltage level , turn on all upper switches– .

2) For voltage level , turn on three upperswitches – and one lower switch .

3) For voltage level , turn on two upper switchesand and two lower switches and .

4) For voltage level , turn on one upperswitch and three lower switches – .

5) For voltage level , turn on all lowerswitches – .

Four complementary switch pairs exist in each phase. The com-plementary switch pair is defined such that turning on one ofthe switches will exclude the other from being turned on. In thisexample, the four complementary pairs are ( ), ( ),( ), and ( ).

Although each active switching device is only required toblock a voltage level of , the clamping diodesmust have different voltage ratings for reverse voltage blocking.Using of Fig. 2(b) as an example, when lower devices

are turned on, needs to block three capacitor voltages,or . Similarly, and need to block , and

needs to block . Assuming that each blocking diodevoltage rating is the same as the active device voltage rating, thenumber of diodes required for each phase will be


Fig. 3. Capacitor-clamped multilevel inverter circuit topologies. (a)Three-level. (b) Five-level.

. This number represents a quadratic increase in. Whenis sufficiently high, the number of diodes required will makethe system impractical to implement. If the inverter runs underPWM, the diode reverse recovery of these clamping diodes be-comes the major design challenge in high-voltage high-powerapplications.

B. Capacitor-Clamped Inverter

Fig. 3 illustrates the fundamental building block of aphase-leg capacitor-clamped inverter. The circuit has beencalled the flying capacitor inverter [1], [5], [6] with independentcapacitors clamping the device voltage to one capacitor voltagelevel. The inverter in Fig. 3(a) provides a three-level outputacrossa andn, i.e., , 0, or . For voltagelevel , switches and need to be turned on; for

, switches and need to be turned on; and forthe 0 level, either pair ( ) or ( ) needs to be turnedon. Clamping capacitor is charged when and areturned on, and is discharged when and are turned on.The charge of can be balanced by proper selection of the0-level switch combination.

The voltage synthesis in a five-level capacitor-clampedconverter has more flexibility than a diode-clamped converter.Using Fig. 3(b) as the example, the voltage of the five-levelphase-lega output with respect to the neutral pointn, , canbe synthesized by the following switch combinations.

1) For voltage level , turn on all upper switches– .

2) For voltage level , there are three combina-tions:

a) , , , ( of upper ’sof );

b) , , , ( of ’s oflower ’s); and

c) , , , ( of upper ’sof ’s of ’s).

3) For voltage level , there are six combinations:

a) , , , ( of upper ’sof ’s);

b) , , , ( of oflower );

c) , , , ( of upper ’sof ’s of ’s of );

d) , , , ( of upper ’sof ’s of );

e) , , , ( of ’s of’s of of lower ’s); and

f) , , , ( of ’s ofof lower ’s).

4) For voltage level , there are three combi-nations:

a) , , , ( of upper ’sof ’s);

b) , , , ( of oflower ’s); and

c) , , , ( of ’s ofof lower ’s).

5) For voltage level , turn on all lowerswitches, – .

In the preceding description, the capacitors with positivesigns are in discharging mode, while those with negativesign are in charging mode. By proper selection of capacitorcombinations, it is possible to balance the capacitor charge.Similar to diode clamping, the capacitor clamping requires alarge number of bulk capacitors to clamp the voltage. Providedthat the voltage rating of each capacitor used is the same as thatof the main power switch, an -level converter will require atotal of clamping capacitors per phaseleg in addition to main dc-bus capacitors.

C. Cascaded Multicell Inverters

A different converter topology is introduced here, which isbased on the series connection of single-phase inverters withseparate dc sources [7]. Fig. 4 shows the power circuit for onephase leg of a nine-level inverter with four cells in each phase.The resulting phase voltage is synthesized by the addition ofthe voltages generated by the different cells. Each single-phasefull-bridge inverter generates three voltages at the output: ,0, and . This is made possible by connecting the capac-itors sequentially to the ac side via the four power switches.The resulting output ac voltage swings from4 to 4with nine levels, and the staircase waveform is nearly sinusoidal,even without filtering.

Another version of cascaded multilevel inverters using stan-dard three-phase two-level inverters has recently been proposed[8]. Its circuit, shown in Fig. 5, uses an output transformer toadd the different voltages. In order for the inverter output volt-ages to be added up, the inverter outputs of the three modulesneed to be synchronized with a separation of 120betweeneach phase. For example, obtaining a three-level voltage be-tween outputsa and b, the voltage is synthesized by

. The phase between and is pro-vided by and through an isolated transformer. With threeinverters synchronized, the voltages , , areall in phase; thus, the output level is simply tripled.

D. Generalized Multilevel Cells

A generalized multilevel inverter topology has previouslybeen presented [19]. The existing multilevel inverters such as


Fig. 4. Cascaded inverter circuit topology and its associated waveform.

Fig. 5. Cascaded inverter with three-phase cells.

diode-clamped and capacitor-clamped multilevel inverters canbe derived from this generalized inverter topology. Moreover,the generalized multilevel inverter topology can balance eachvoltage level by itself regardless of load characteristics. There-fore, the generalized multilevel inverter topology provides atrue multilevel structure that can balance each dc voltage levelautomatically at any number of levels, regardless of active orreactive power conversion, and without any assistance fromother circuits. Thus, in principle, it provides a complete multi-level topology that embraces the existing multilevel inverters.

Fig. 6 shows the P2 multilevel inverter structure per phase leg.Each switching device, diode, or capacitor’s voltage is 1, i.e.,

of the dc-link voltage. Any inverter with any numberof levels, including the conventional two-level inverter can beobtained using this generalized topology.

As an application example, a four-level bidirectional dc/dcconverter, shown in Fig. 7, is suitable for the dual-voltagesystem to be adopted in future automobiles. The four-leveldc/dc converter has a unique feature, which is that no magneticcomponents are needed. From this generalized multilevelinverter topology, several new multilevel inverter structures canbe derived [19].

Fig. 6. Generalized P2 multilevel inverter structure.

Fig. 7. Application example: a four-level P2 converter for the dual-voltagesystem in automobiles.

E. Emerging Multilevel Inverter Topologies

1) Mixed-Level Hybrid Multilevel Cells:For high-voltagehigh-power applications, it is possible to adopt multileveldiode-clamped or capacitor-clamped inverters to replace thefull-bridge cell in a cascaded inverter [20]. The reason fordoing so is to reduce the amount of separate dc sources. Thenine-level cascaded inverter shown in Fig. 4 requires four sepa-rate dc sources for one phase leg and twelve for a three-phaseinverter. If a three-level inverter replaces the full-bridge cell,the voltage level is effectively doubled for each cell. Thus, toachieve the same nine voltage levels for each phase, only twoseparate dc sources are needed for one phase leg and six for athree-phase inverter. The configuration can be considered ashaving mixed-level hybrid multilevel cells because it embedsmultilevel cells as the building block of the cascaded inverter.Fig. 8 shows the nine-level cascaded inverter incorporating athree-level capacitor-clamped inverter as the cell. It is obviousthat a diode-clamped inverter can replace the capacitor-clampedinverter to be a mixed-level hybrid multilevel cell.

2) Asymmetric Hybrid Multilevel Cells:In previous de-scriptions, the voltage levels of the cascade inverter cells equaleach other. However, it is possible to have different voltagelevels among the cells [21], [22], and the circuit can be called asasymmetric hybrid multilevel inverter. Fig. 9 shows an exampleof having two separate dc-bus levels, one with , and the


Fig. 8. A mixed-level hybrid cell configuration using the thee-leveldiode-clamped inverter as the cascaded inverter cell to increase the voltagelevels.

Fig. 9. Asymmetric hybrid cascaded inverter cell arrangement with differentvoltage levels.

other with . Depending on the availability of dc sources,the voltage levels are not limited to a specific ratio. This featureallows more levels to be created in the output voltage, andthus reduces the harmonic contents with less cascaded cellsrequired.

Even with the same voltage level among them, it is also pos-sible to use high-frequency PWM for one cell, while the otherswitches at a lower rate. Fig. 10 shows an example with two dif-ferent devices. The top full-bridge cell uses the insulated gatebipolar transistor (IGBT), and the low cell uses the gate-turn-offthyristor (GTO) as its switching device. The GTO-based cellswitches at a lower frequency, typically the fundamental fre-quency, and the IGBT-based cell switches at a PWM frequencyto smooth the waveform [21], [22].

3) Soft-Switched Multilevel Inverters:There are numerousways of implementing soft-switching methods to reduce theswitching loss and to increase efficiency for different multilevelinverters. For the cascaded inverter, because each inverter cell isa two-level circuit, the implementation of soft switching is not

Fig. 10. Asymmetric cascade inverter cell arrangement with differentswitching frequencies.

Fig. 11. Zero-voltage-switching capacitor-clamped inverter circuit.

at all different from that of conventional two-level inverters. Forcapacitor- or diode-clamped inverters, however, the choices ofsoft-switching circuit can be found with different circuit combi-nations [23]–[29]. Although zero-current switching is possible[30], most literatures proposed zero-voltage-switching types in-cluding auxiliary resonant commutated pole (ARCP), coupledinductor with zero-voltage transition (ZVT), and their combi-nations. Fig. 11 shows an example of combining the ARCPand coupled-inductor ZVT techniques for a capacitor-clampedthree-level inverter.

The auxiliary switches , , , and are usedto assist the inner main switches and to achieve softswitching. With as the coupled inductor, the bridge-typecircuit formed by , , , and forms a two-levelcoupled-inductor ZVT. The basic principle of a two-level ZVTcan be found in [31]–[35]. For the outer main switches, the softswitching relies on and , , , , , coupledinductor , and split-capacitor pair to form an ARCPtype soft-switching inverter. Detailed soft-switching circuitoperation for inner devices and outer devices can be found in[24], [26].

III. CONTROL AND MODULATION STRATEGIES

A. Classification of Modulation Strategies

The modulation methods used in multilevel inverters can beclassified according to switching frequency, as shown in Fig. 12[36], [37]. Methods that work with high switching frequencies


Fig. 12. Classification of multilevel modulation methods.

have many commutations for the power semiconductors inone period of the fundamental output voltage. A very popularmethod in industrial applications is the classic carrier-based si-nusoidal PWM (SPWM) that uses the phase-shifting techniqueto reduce the harmonics in the load voltage [7], [38], [39].Another interesting alternative is the SVM strategy, which hasbeen used in three-level inverters [36].

Methods that work with low switching frequencies generallyperform one or two commutations of the power semiconduc-tors during one cycle of the output voltages, generating a stair-case waveform. Representatives of this family are the multilevelselective harmonic elimination [40], [41] and the space-vectorcontrol (SVC) [42].

B. Multilevel SPWM

Several multicarrier techniques have been developed to re-duce the distortion in multilevel inverters, based on the classicalSPWM with triangular carriers. Some methods use carrier dis-position and others use phase shifting of multiple carrier signals[38], [43], [44]. Fig. 13(a) shows the typical voltage generatedby one cell for the inverter shown in Fig. 4 by comparing a si-nusoidal reference with a triangular carrier signal.

A number of –cascaded cells in one phase with their car-riers shifted by an angle and using the samecontrol voltage produce a load voltage with the smallest dis-tortion. The effect of this carrier phase-shifting technique canbe clearly observed in Fig. 14. This result has been obtainedfor the multi-cell inverter in a seven-level configuration, whichuses three series-connected cells in each phase. The smallest dis-tortion is obtained when the carriers are shifted by an angle of

.A very common practice in industrial applications for the

multilevel inverter is the injection of a third harmonic in eachcell, as shown in Fig. 13(b), to increase the output voltage [7],[20]. Another advantageous feature of multilevel SPWM is thatthe effective switching frequency of the load voltage istimesthe switching frequency of each cell, as determined by its car-rier signal. This property allows a reduction in the switchingfrequency of each cell, thus reducing the switching losses.

C. SVM

The SVM technique can be easily extended to all multilevelinverters [45]–[51]. Fig. 15 shows space vectors for the tradi-tional two-, three-, and five-level inverters. These vector dia-

Fig. 13. Inverter cell voltages. (a) Output voltage and reference with SPWM.(b) Output voltage and reference with injection of sinusoidal third harmonic.

Fig. 14. Total voltage of three cells in series connection for different phasedisplacement in the carriers.

grams are universal regardless of the type of multilevel inverter.In other words, Fig. 15(c) is valid for five-level diode-clamped,capacitor-clamped, or cascaded inverter. The adjacent three vec-tors can synthesize a desired voltage vector by computing theduty cycle ( , , and ) for each vector

(3)

Space-vector PWM methods generally have the following fea-tures: good utilization of dc-link voltage, low current ripple, andrelatively easy hardware implementation by a digital signal pro-cessor (DSP). These features make it suitable for high-voltagehigh-power applications.

As the number of levels increases, redundant switching statesand the complexity of selecting switching states increase dra-matically. Some authors have used decomposition of the five-level space-vector diagram into two three-level space-vector di-agrams with a phase shift to minimize ripples and simplify con-


Fig. 15. Space-vector diagram: (a) two-level, (b) three-level, and (c) five-levelinverter.

trol [48]. Additionally, a simple space-vector selection methodwas introduced without duty cycle computation of the adjacentthree vectors [37].

D. Selective Harmonic Elimination

Fig. 16 shows a generalized quarter-wave symmetric stepped-voltage waveform synthesized by a -level inverter,where is the number of switching angles. By applying Fourierseries analysis, the amplitude of any odd harmonic of thestepped waveform can be expressed as (4), whereas the ampli-tudes of all even harmonics are zero

(4)

where is the level of dc voltage, is an odd harmonicorder, is the number of switching angles, and is the thswitching angle. According to Fig. 16, to must satisfy

.To minimize harmonic distortion and to achieve adjustable

amplitude of the fundamental component, up to harmonic

Fig. 16. Generalized stepped-voltage waveform.

contents can be removed from the voltage waveform. In gen-eral, the most significant low-frequency harmonics are chosenfor elimination by properly selecting angles among different-level inverters, and high-frequency harmonic components canbe readily removed by using additional filter circuits. Accordingto (4), to keep the number of eliminated harmonics at a con-stant level, all switching angles must be less than. How-ever, if the switching angles do not satisfy the condition, thisscheme no longer exists. As a result, this modulation strategybasically provides a narrow range of modulation index, whichis its main disadvantage. For example, in a seven-level equallystepped waveform, its modulation index is only available from0.5 to 1.05. At modulation indexes lower than 0.5, if this schemeis still applied, the allowable harmonic components to be elim-inated will reduce from 2 to 1. The total harmonic distortion(THD) increases correspondingly.

In order to achieve a wide range of modulation indexes withminimized THD for the synthesized waveforms, a generalizedselected harmonic modulation scheme was proposed [40], [41].The method can be illustrated by Fig. 17, in which the positivehalf-cycle of seven-level stepped waveforms are shown with dif-ferent modulation index levels. In this case, the range of mod-ulation indices can be divided into three levels, such as high,middle, and low. An output waveform with a high modulationindex level is shown in Fig. 17(a). Whenever is greater than

, this waveform no longer exists. Therefore, an output wave-form shown in Fig. 17(b), which gives middle modulation indexlevel, will be applied instead. When the switching anglesto

in Fig. 17(b) are not converged at a low modulation indexlevel, the output waveform shown in Fig. 17(c) will replace it.In general, a stepped waveform, which comprisesswitchingangles, can be divided into modulation index levels. By usingthis technique, low switching frequencies with minimized har-monics in the output waveforms can be achieved with wide mod-ulation indexes.

Through mathematical manipulation and observation ofFig. 17(a)–(c), a generalized harmonic expression for multi-level stepped voltage has been derived [41] and is expressed asthe following equation:

(5)

In this expression, the positive sign implies the rising edge, andthe negative sign implies the falling edge.


Fig. 17. A positive half-cycle of a seven-level stepped waveform with differentmodulation indexes. (a) High modulation index. (b) Middle modulation index.(c) Low modulation index.

E. SVC

A conceptually different control method for multilevelinverters, based on the space-vector theory, has been intro-duced [37]. This control strategy, called SVC, works with lowswitching frequencies and does not generate the mean value ofthe desired load voltage in every switching interval, as is theprinciple of SVM.

Fig. 18 shows the 311 different space vectors generated by an11-level inverter. The reference load voltage vector is alsoincluded in this figure. The main idea in SVC is to deliver tothe load a voltage vector that minimizes the space error or dis-tance to the reference vector . The high density of vectorsproduced by the 11-level inverter (see Fig. 18.) will generateonly small errors in relation to the reference vector; it is, there-fore, unnecessary to use a more complex modulation schemeinvolving the three vectors adjacent to the reference.

The shaded hexagon of Fig. 18 shows the boundary of highestproximity, which means that when the reference voltageislocated in this area, vector must be selected, because it hasthe greatest proximity to the reference.

Fig. 19(a) presents the voltage generated by one cell in aneleven-level multicell inverter with five cells per phase and anoutput frequency of 50 Hz. The load voltage of the inverterfor the same frequency and modulation index 0.99 is shown inFig. 19(b).

Finally, Fig. 20 shows the reference vector and the vectorsgenerated by the inverter using SVC [37]. This method is simpleand attractive for high number of levels. As the number of levelsdecreases, the error in terms of the generated vectors with re-spect to the reference will be higher; this will increase the loadcurrent ripple.

Fig. 18. Load voltage space vectors generated by an 11-level inverter.

Fig. 19. Voltages generated by an 11-level inverter with SVC. (a) One-cellvoltage. (b) Resulting load voltage.

F. Direct Torque Control (DTC)

The DTC technique has been developed for low-voltage two-level inverters as an alternative to the field oriented method toeffectively control torque and flux in ac drives [52]. DTC andhysteresis current control techniques have also been applied inmultilevel inverters [53]. It must be noticed that one major man-ufacturer has been selling medium-voltage three-level diode-clamped inverters controlled with DTC [54].

G. Capacitor Balancing Techniques

In [55], the voltage unbalancing problem and the mechanismof the diode-clamped multilevel inverter were discussed. Thepaper demonstrated that the diode-clamped multilevel invertercould not have balanced voltages for real power conversionwithout sacrificing output voltage performance. Thus, thepaper proposed that the diode-clamped multilevel inverter beapplied to reactive and harmonic compensation without voltage


Fig. 20. Reference and output voltage vectors in an 11-level inverter withSVC.

balancing problem. Reference [56] suggested that the voltageunbalance problem could be solved by using a back-to-backrectifier/inverter system and proper voltage balancing control.Other papers [57]–[59] suggested the use of additional voltagebalancing circuits, such dc chopper, etc.

The capacitor-clamped structure was originally proposed forhigh-voltage dc/dc conversions [60]. It is easy to balance thevoltages for such applications because the load current is dc.For the capacitor-clamped multilevel inverter, voltage balancingis relatively complicated [60], [61]. It has been shown theoret-ically that the capacitor-clamped inverter cannot have self-bal-anced voltage when applied to power conversion in which noreal power is involved, such as reactive power compensation.However, since each phase leg has its own floating capacitorsthat handle the phase current, the voltage balancing and ripplebecome troublesome.

The cascaded multilevel inverter was first introduced formotor drive applications, in which an isolated and separatedc source is needed for each H-bridge unit [7]. However,another paper presented the idea of using cascade multilevelinverter for reactive and harmonic compensation, from whichisolated dc sources can be omitted [56]. Additional workfurther demonstrated that the cascaded inverter is suitable foruniversal power conditioning of power systems, especiallyfor medium-voltage systems [62], [63]. The inverter provideslower costs, higher performance, less electromagnetic interfer-ence (EMI), and higher efficiency than the traditional PWMinverter for power line conditioning applications, both seriesand parallel compensation. Although the cascaded inverter hasan inherent self-balancing characteristic, because of the circuitcomponent losses and limited controller resolution, a slightvoltage imbalance can occur. A simple control scheme, whichensures dc voltage balance, has been proposed for reactive andharmonic compensation [56]. Fig. 21 shows its control blockdiagram that contains a proportional–integral (PI) regulator toadjust the trigger angle and to ensure zero steady-state errorbetween the reference dc voltage and the dc-bus voltage.

Fig. 21. Control diagram of the 11-level cascaded inverter.

Fig. 22. Vienna rectifier phase-leg structure.

IV. I NDUSTRIAL APPLICATIONS AND TECHNOLOGICAL

ASPECTS

A. Multilevel Rectifier

Traditionally, multipulse rectifiers have been used for the re-duction of harmonics in the line current. These multipulse (12-pulse, 18-pulse, and so on) rectifiers use transformers for phaseshifting in order to eliminate harmonics. To eliminate the phase-shift transformers, multilevel rectifiers have been proposed.

For those applications that require no regenerative capability,simplified (or reduced) multilevel rectifiers have been proposedin [64]. This specific rectifier, named the Vienna rectifier, hasbeen used for telecommunication power supplies. Fig. 22 showsthe per-phase leg structure for a three-level Vienna rectifier.Some reduced-parts-count multilevel rectifiers for the numbermore than three levels have been proposed [65].

B. DC/DC Converters

The phase voltage of a multilevel diode-clamped or capac-itor-clamped inverter resembles that of a full-bridge phase-shift-


Fig. 23. Three-level capacitor-clamped inverter for dc–dc converterapplication. (a) Circuit diagram. (b) Gating and output waveforms.

modulated dc/dc converter [66]. Fig. 23(a) shows a three-leveldc/dc converter based on a capacitor-clamped inverter circuitalong with diode clamping to ensure neutral-point voltage bal-ance [67], [68]. The same as the capacitor-clamped inverter, thisconverter only allows certain switch pairs to be turned on simul-taneously. The switch pair { } yields , { }yields , and { } and { } yield zero output.By applying gate pulses sequentially, as shown in Fig. 23(b), athree-level output voltage across the transformer primary can beobtained. With phase-shift operation, this circuit operates inher-ently under the soft-switching condition.

C. Large Motor Drives With Nonregenerative Front Ends

Diode-clamped three-level inverters are now widely appliedin medium-voltage (2.3, 3.3, 4.16, and even 6 kV) applications,using an IGBT with forced-air cooling. These applicationscover a wide range of high-power loads including fans, pumps,blowers, compressors, and conveyors.

An important issue in the application of these inverters isthe injection of current harmonics into the power supply dueto both the high power of the drive and the capacitive filters inthe dc link, which increase the distortion of the input current. A12-pulse configuration of the input rectifier, as shown in Fig. 24,is a standard solution for reducing the input current harmonics.Some manufacturers include an 18-pulse and 24-pulse rectifierto improve the quality of the input current.

Fig. 25 presents a three-level inverter with capacitor-clampedtopology and 18-pulse configuration of the input rectifier [69].The secondary voltages are shifted by 20from each other. Withthis type of input rectifier, the harmonics in the input currents aredrastically reduced, achieving a THD of less than 1.55% [69].

Fig. 26 shows a seven-level cascade multicell inverter used innonregenerative drives for 2.3-kV networks. This inverter usesthree cells in each phase. The input part of each cell has a three-

Fig. 24. Three-level diode-clamped inverter with 12-pulse input rectifier.

Fig. 25. Three-level capacitor-clamped inverter with 18-pulse input rectifier.

Fig. 26. Seven-level cascaded inverter with nonregenerative rectifier.

phase diode rectifier, which does not allow the regeneration ofpower. Table I presents the number of cells used in each phasefor different motor voltages, as reported by one manufacturer[7].

The high quality of the input current assures compliance withIEEE Standard 519–1992. In the case of 4.16-kV inverters withfive cells per phase, the quality of the output voltage is very highwith a voltage distortion THD of 10%. In this 11-level inverter,the input current of the inverter has a 30-pulse waveform and aTHD of 1 [7].


TABLE ICASCADED INVERTERSUSED IN MEDIUM-VOLTAGE DRIVES [7]

D. Large Motor Drives With Regenerative Front Ends

The use of a three-level active front end (AFE) at the inputside of a three-level diode-clamped inverter has become avery popular solution for high-power regenerative loads. Thissolution, presented in Fig. 27, allows the regeneration of fullmotor power with reduced harmonics and high power factor.Drives with three-level AFE are used in laminators [70],high-power downhill conveyors [71], and other regenerativehigh-power loads.

A very interesting application of this technology in which twothree-level AFEs are used in a so-called tandem configurationis shown in Fig. 28 [71]. This drive uses GTO technology and,for this reason, an operation with low switching frequency ishighly desirable. The selective harmonic-elimination method isused with three commutation angles (, , and ) in eachAFE in order to eliminate harmonics 11 and 13. The equationsto achieve this purpose are

(6)

(7)

(8)

where is the modulation index and is the voltage in eachdc-link capacitor.

The wye–wye and wye–delta connection in the input trans-formers produces a 30displacement in the input voltages of theAFEs, eliminating all harmonics of order odd :5, 7, 17, 19, 29, and 31. In this way, the first harmonics are ofthe order 23 and 25. An important reduction of the input currentharmonics, working with a very low switching frequency, is ob-tained with this method.

Although this multipulse transformer allows thephase-shifted currents to be summed together for a nearsinusoidal input current, the major difficulty is the design ofthe transformer. With irrational turns ratios, it is possible toproduce undesirable interharmonic contents. Fig. 29 shows asolution using an active filter circuit as the regenerative frontend [14]. In this circuit, the transformer does not need to haveirrational turns ratios because the secondary winding currentis compensated by an active filter. The active filter also allowspower flow to be reversed, which solves the problem found inFig. 26.

The regenerative block shown in Fig. 29 has limited ca-pability because the active filter is normally designed witha smaller power rating. In certain applications in which theregenerative block also needs rated capability, the circuit shownin Fig. 29 would not be applicable. A more general-purposeregenerative four-quadrant-type configuration is shown inFig. 30 [16]. In this circuit, each power module contains anAFE converter and a full-bridge inverter. The AFE convertercorrects the power factor and eliminates the harmonics, thus,the transformer can be designed in a conventional way, similarto the one shown in Fig. 29. It allows all the regenerative powerto be pumped back to the source because the AFE converterneeds to be designed with full power rating. The only drawbackto this AFE-based cascaded inverter is that it requires highnumber of devices. The use of single-phase AFEs at the lineside of each cell has been considered as an alternative to sparepower semiconductors [72]. However, this circuit imposes re-strictions to the number of cells that can be connected in seriesto eliminate low-frequency harmonics in the input current.

E. Applications in Power Systems

When the number of levels is greater than three, both thediode-clamped and cascaded multilevel inverters have equiv-alently separate dc sources for each level in order to enablepower conversion involving real power such as in motor drives[11], [57]. However, as mentioned previously, both invertershave a perfect niche in harmonic and reactive power compen-sation [55], [62], [63]. The capacitor-clamped inverter cannothave balanced voltage for power conversion involving only re-active power [61], thus, it is not suited for reactive power com-pensation.

The first unified power-flow controller (UPFC) in the worldwas based on a diode-clamped three-level inverter [73]. TheUPFC is comprised of the back-to-back connection of two iden-tical GTO thyristor-based three-level converters, each rated at160 MVA; it was commissioned in mid-1998 at the Inez Sta-tion of American Electric Power (AEP) in Kentucky for voltagesupport and power-flow control. Fig. 31 shows the system con-figuration.

On the other hand, the cascaded multilevel inverter is bestsuited for harmonic/reactive compensation and other utilityapplications [13], [62], [63], since each H-bridge inverter unitcan balance its dc voltage without requiring additional isolatedpower sources. GEC Alsthom T&D has commercialized thecascaded multilevel inverter for reactive power compensa-tion/generation (STATCOM) [74].

V. FUTURE TRENDS

By looking at the number of papers published in recentyears, it is easy to conclude that multilevel inverter research anddevelopment activities are experiencing an explosive rate ofgrowth. A trend of having more and more multilevel invertersis obvious. Although this paper has focused on multilevel in-verter circuit topology, control, and applications, there is otherresearch and development in related areas, such as high-voltagehigh-power semiconductor devices, sensors, high-speed DSPs,thermal management, and packaging. It is difficult to include


Fig. 27. Three-level AFE and inverter.

Fig. 28. Two parallel-connected three-level AFEs.

Fig. 29. Cascaded multicell inverter regenerative blocks.

all the related technologies in one paper; however, thosetechnologies related to multilevel inverter development shouldnot be neglected from the ongoing development. Based onthe progress of semiconductor devices and advanced circuittopologies, future trends can be observed in the following areas.

Fig. 30. Cascaded regenerative inverter with three-phase AFEs.

Fig. 31. System configuration of the UPFC installed at Inez.


A. Applications for Distribution Voltage Level

There is a strong demand to push voltage-source inverters(VSIs) into distribution voltage level, which is between 11–16kV, or typically 13.8 kV. Currently, the power electronics for dis-tribution and transmission voltage levels are mainly dominatedby current source converters, which use thyristor devices withbuilt-in reverse voltage blocking capability. The main problemswith thyristors are their sluggish switching speeds and their in-ability to gate off. With the use of gate-turn-off high-voltagesemiconductor devices in multilevel inverters, the widespreaduse of VSIs in distribution voltage level can be easily expected.

B. Advanced High-Voltage High-Power SemiconductorDevices

The availability of higher-voltage devices allows higheroperating voltages with fewer inverter levels. The majorcontenders in the device arena are integrated-gate-commutatedthyristor (IGCT) [75], [76], 3.3- and 6.5-kV high-voltage IGBT(HV-IGBT) [77], and emitter turn-off (ETO) thyristor [78]. Aspower level increased with new devices, the multilevel inverterpower-handling capability is also proportionally increased.With the use of these high voltage devices, an inverter can easilyachieve 5 MW with only three levels required. The applicationto the distribution voltage level can be achieved with less thanfive levels when the above-mentioned high-voltage devices areused.

C. Use of Optical Fibers for Sensors and Controls

For a scaled-down version multilevel inverter prototype andits control implementation, the wiring is short, the parasitic isminimum, and the isolation is not an issue. However, for a high-voltage system, the CM voltage level and the distance betweenpower modules and the DSP controller become major problemsin the inverter design. The CM voltage level can easily produceenough noise and upset the control circuit and gate drives. Thewiring from controller to power modules for a multimegawattinverter is also a problem, as it can be as long as tens of meters,which can either be the source of noise or be upset by noise. Afuture trend is to apply fiber-optic technologies for sensors, gatedrive controllers, and communications.

D. Thermal Management

The conventional disc-type thyristors are typically cooled bycirculating water through their clamping assemblies. This re-quires substantial effort to make sure that the water is deionizedand well circulated with a sufficient flow rate. The water-cooledsystem is difficult to move around because the water can easilyleak. For high-voltage systems, the insulation becomes a con-cern if the water deionizing system is not functioning. Withthe module-type package for high-voltage IGBTs, however, thecooling is much more flexible. Other cooling techniques, suchas forced air and heat pipe, are gaining more acceptability in in-dustry applications.

E. Distributed Energy Applications

Distributed energy systems, mostly those using alternativeenergies such as photovoltaic panels and fuel cells, can be easily

configured with a separate source connected through the powerconversion circuits used as an energy module or building blockto provide individual output. A cascaded inverter can then beconfigured with multiple modules. Such a system does not needa transformer to provide isolation, and the system can be con-structed in a cost effective manner.

VI. CONCLUSION

This paper has provided a brief summary of multilevelinverter circuit topologies and their control strategies. Dif-ferent applications using different inverter circuits were alsodiscussed. As mentioned in Section I, an early patent for thecascaded multilevel inverter can be traced back to 1975. How-ever, the commercial products that utilize this superior circuittopology were not available until the mid-1990s. Today, moreand more commercial products are based on the multilevelinverter structure, and more and more worldwide researchand development of multilevel inverter-related technologies isoccurring. This paper cannot cover or reference all the relatedwork, but the fundamental principle of different multilevelinverters has been introduced systematically. The intention ofthe authors was simply to provide groundwork to readers in-terested in looking back on the evolution of multilevel invertertechnologies, and to consider where to go from here.

REFERENCES

[1] J. S. Lai and F. Z. Peng, “Multilevel converters–A new breed of powerconverters,”IEEE Trans. Ind. Applicat., vol. 32, pp. 509–517, May/June1996.

[2] L. Tolbert, F.-Z. Peng, and T. Habetler, “Multilevel converters for largeelectric drives,”IEEE Trans. Ind. Applicat., vol. 35, pp. 36–44, Jan./Feb.1999.

[3] R. Teodorescu, F. Beaabjerg, J. K. Pedersen, E. Cengelci, S. Sulistijo,B. Woo, and P. Enjeti, “Multilevel converters — A survey,” inProc.European Power Electronics Conf. (EPE’99), Lausanne, Switzerland,1999, CD-ROM.

[4] A. Nabae, I. Takahashi, and H. Akagi, “A new neutral-point clampedPWM inverter,” IEEE Trans. Ind. Applicat., vol. IA-17, pp. 518–523,Sept./Oct. 1981.

[5] T. A. Meynard and H. Foch, “Multi-level choppers for high voltage ap-plications,” Eur. Power Electron. Drives J., vol. 2, no. 1, p. 41, Mar.1992.

[6] C. Hochgraf, R. Lasseter, D. Divan, and T. A. Lipo, “Comparison ofmultilevel inverters for static var compensation,” inConf. Rec. IEEE-IASAnnu. Meeting, Oct. 1994, pp. 921–928.

[7] P. Hammond, “A new approach to enhance power quality for mediumvoltage ac drives,”IEEE Trans. Ind. Applicat., vol. 33, pp. 202–208,Jan./Feb. 1997.

[8] E. Cengelci, S. U. Sulistijo, B. O. Woom, P. Enjeti, R. Teodorescu, andF. Blaabjerge, “A new medium voltage PWM inverter topology for ad-justable speed drives,” inConf. Rec. IEEE-IAS Annu. Meeting, St. Louis,MO, Oct. 1998, pp. 1416–1423.

[9] R. H. Baker and L. H. Bannister, “Electric power converter,” U.S. Patent3 867 643, Feb. 1975.

[10] R. H. Baker, “Switching circuit,” U.S. Patent 4 210 826, July 1980.[11] , “Bridge converter circuit,” U.S. Patent 4 270 163, May 1981.[12] P. W. Hammond, “Medium voltage PWM drive and method,” U.S. Patent

5 625 545, Apr. 1997.[13] F. Z. Peng and J. S. Lai, “Multilevel cascade voltage-source inverter with

separate DC sources,” U.S. Patent 5 642 275, June 24, 1997.[14] P. W. Hammond, “Four-quadrant AC-AC drive and method,” U.S. Patent

6 166 513, Dec. 2000.[15] M. F. Aiello, P. W. Hammond, and M. Rastogi, “Modular multi-level

adjustable supply with series connected active inputs,” U.S. Patent6 236 580, May 2001.

[16] , “Modular multi-level adjustable supply with parallel connectedactive inputs,” U.S. Patent 6 301 130, Oct. 2001.


[17] J. P. Lavieville, P. Carrere, and T. Meynard, “Electronic circuit for con-verting electrical energy and a power supply installation making usethereof,” U.S. Patent 5 668 711, Sept. 1997.

[18] T. Meynard, J.-P. Lavieville, P. Carrere, J. Gonzalez, and O. Bethoux,“Electronic circuit for converting electrical energy,” U.S. Patent5 706 188, Jan. 1998.

[19] F. Z. Peng, “A generalized multilevel inverter topology with self voltagebalancing,”IEEE Trans. Ind. Applicat., vol. 37, pp. 611–618, Mar./Apr.2001.

[20] W. A. Hill and C. D. Harbourt, “Performance of medium voltage multi-level inverters,” inConf. Rec. IEEE-IAS Annu. Meeting, Pheonix, AZ,Oct. 1999, pp. 1186–1192.

[21] M. D. Manjrekar, P. K. Steimer, and T. A. Lipo, “Hybrid multilevelpower conversion system: a competitive solution for high-power appli-cations,” IEEE Trans. Ind. Applicat., vol. 36, pp. 834–841, May/June2000.

[22] R. Lund, M. Manjrekar, P. Steimer, and T. Lipo, “Control strategy for ahybrid seven-level inverter,” inProc. European Power Electronics Conf.(EPE‘99), Lausanne, Switzerland, 1999, CD-ROM.

[23] B. M. Song, S. Gurol, C. Y. Jeong, D. W. Yoo, and J. S. Lai, “Asoft-switching high-voltage active power filter with flying capacitorsfor urban maglev system applications,” inConf. Rec. IEEE-IAS Annu.Meeting, Chicago, IL, Sept. 2001, pp. 1461–1469.

[24] B. M. Song and J. S. Lai, “A multilevel soft-switching inverter withinductor coupling,”IEEE Trans. Ind. Applicat., vol. 37, pp. 628–636,Mar./Apr. 2001.

[25] X. Yuan and G. Orgimeister, “ARCPI resonant snubber for the neutral-point-clamped (NPC) inverter,”IEEE Trans. Ind. Applicat., vol. 36, pp.586–595, Mar./Apr. 2000.

[26] X. Yuan and I. Barbi, “Zero voltage switching for three level capacitorclamping inverter,”IEEE Trans. Power Electron., vol. 14, pp. 771–781,July 1999.

[27] , “A transformer assisted zero-voltage switching scheme for theneutral-point-clamped (NPC) inverter,” inProc. IEEE APEC’99, 1999,pp. 1259–1265.

[28] F. R. Dijkhuizen, J. L. Duarte, and W. D. H. van Gorningen, “Multi-level converter with auxiliary resonant commutated pole,” inConf. Rec.IEEE-IAS Annu. Meeting, Oct. 1998, pp. 1440–1446.

[29] R. Teichmann, K. O’Brian, and S. Bernet, “Comparison of multilevelARCP topologies,” inProc. Int. Power Electronics Conf., Tokyo, Japan,2000, pp. 2035–2040.

[30] D. Peng, D. H. Lee, F. C. Lee, and D. Borojevic, “Modulation and controlstrategies of ZCT three-level choppers for SMES application,” inProc.IEEE PESC, Galway, Ireland, June 2000, pp. 121–126.

[31] W. McMurray, “Resonant snubbers with auxiliary switches,”IEEETrans. Ind. Applicat., vol. 29, pp. 355–362, Mar./Apr. 1993.

[32] R. W. DeDoncker and J. P. Lyons, “The auxiliary quasi-resonant dc linkinverter,” inProc. IEEE PESC’91, June 1991, pp. 248–253.

[33] J. S. Lai, “Fundamentals of a new family of auxiliary resonant snubberinverters,” inProc. IEEE IECON’97, New Orleans, LA, Nov. 1997, pp.640–645.

[34] S. Frame, D. Katsis, D. H. Lee, D. Borojevic, and F. C. Lee, “A three-phase zero-voltage-transition inverter with inductor feedback,” inProc.1996 VPEC Seminar, Blacksburg, VA, Sept. 1996, pp. 189–193.

[35] J. P. Gegner and C. Q. Lee, “Zero-voltage transition converters usinginductor feedback technique,” inProc. IEEE APEC’94, Orlando, FL,Mar. 1994, pp. 862–868.

[36] N. Celanovic and D. Boroyevic, “A fast space vector modulation al-gorithm for multilevel three-phase converters,” inConf. Rec. IEEE-IASAnnu. Meeting, Phoenix, AZ, Oct. 1999, pp. 1173–1177.

[37] J. Rodríguez, P. Correa, and L. Morán, “A vector control technique formedium voltage multilevel inverters,” inProc. IEEE APEC, Anaheim,CA, Mar. 2001, pp. 173–178.

[38] L. Tolbert and T. G. Habetler, “Novel multilevel inverter carrier-basedPWM method,”IEEE Trans. Ind. Applicat., vol. 35, pp. 1098–1107,Sept./Oct. 1999.

[39] Y. Liang and C. O. Nwankpa, “A new type of STATCOM Based oncascading voltage-source inverters with phase-shifted unipolar SPWM,”IEEE Trans. Ind. Applicat., vol. 35, pp. 1118–1123, Sept./Oct. 1999.

[40] L. Li, D. Czarkowski, Y. Liu, and P. Pillay, “Multilevel selectiveharmonic elimination PWM technique in series-connected voltageinverters,” in Conf. Rec. IEEE-IAS Annu. Meeting, Oct. 1998, pp.1454–1461.

[41] S. Sirisukprasert, J. S. Lai, and T. H. Liu, “Optimum harmonic reduc-tion with a wide range of modulation indexes for multilevel converters,”in Conf. Rec. IEEE-IAS Annu. Meeting, Rome, Italy, Oct. 2000, pp.2094–2099.

[42] J. Rodríguez, L. Morán, C. Silva, and P. Correa, “A high performancevector control of a 11-level inverter,” inProc. 3rd Int. Power Electronicsand Motion Control Conf., Beijing, China, Aug. 2000, pp. 1116–1121.

[43] B. N. Mwinyiwiwa, Z. Wolanski, and B. T. Ooi, “Microprocessor imple-mented SPWM for multiconverters with phase-shifted triangle carriers,”in Conf. Rec. IEEE-IAS Annu. Meeting, New Orleans, LA, Oct. 1997, pp.1542–1549.

[44] V. G. Agelidis and M. Calais, “Application specific harmonic perfor-mance evaluation of multicarrier PWM techniques,” inProc. IEEEPESC’98, Fukuoka, Japan, May 1998, pp. 172–178.

[45] Y. H. Lee, R. Y. Kim, and D. S. Hyun, “A novel SVPWM strategy con-sidering DC-link balancing for a multi-level voltage source inverter,” inProc. IEEE APEC’98, 1998, pp. 509–514.

[46] B. P. McGrath, D. G. Holmes, and T. A. Lipo, “Optimized space vectorswitching sequences for multilevel inverters,” inProc. IEEE APEC,Anaheim, CA, Mar. 4–8, 2001, pp. 1123–1129.

[47] J. Mahdavi, A. Agah, A. M. Ranjbar, and H. A. Toliyat, “Extension ofPWM space vector technique for multilevel current-controlled voltagesource inverters,” inProc. IEEE IECON’99, San Jose, CA, Nov. 29–Dec. 3, 1999, pp. 583–588.

[48] L. Li, D. Czarkowski, Y. Liu, and P. Pillay, “Multilevel space vectorPWM technique based on phase-shift harmonic suppression,” inProc.IEEE APEC, New Orleans, LA, Feb. 2000, pp. 535–541.

[49] M. Manjrekar and G. Venkataramanan, “Advanced topologies andmodulation strategies for multilevel inverters,” inProc. IEEE PESC’96,Baveno, Italy, June 1996, pp. 1013–1018.

[50] D. G. Holmes and B. P. McGrath, “Opportunities for harmonic cancel-lation with carrier-based PWM for two-level and multilevel cascadedinverters,”IEEE Trans. Ind. Applicat., vol. 37, pp. 574–582, Mar./Apr.2001.

[51] D. W. Kang et al., “Improved carrier wave-based SVPWM methodusing phase voltage redundancies for generalized cascaded multilevelinverter topology,” inProc. IEEE APEC, New Orleans, LA, Feb. 2000,pp. 542–548.

[52] M. Deppenbrock, “Direct self control (DSC) of inverter-fed inductionmachine,”IEEE Trans. Power Electron., vol. 3, pp. 420–429, July 1988.

[53] A. M. Walczyna and R. J. Hill, “Space vector PWM strategy for 3-levelinverters with direct self-control,” inProc. 5th European Conf. PowerElectronics, Brighton, U.K, 1993, pp. 152–157.

[54] P. Lataire, “White paper on the new ABB medium voltage drive system,using IGCT power semiconductors and direct torque control,”EPE J.,vol. 7, no. 3, pp. 40–45, Dec. 1998.

[55] F. Z. Peng and J. S. Lai, “A static var generator using a staircase wave-form multilevel voltage-source converter,” inProc. Seventh Int. PowerQuality Conf., Dallas, TX, Sept. 1994, pp. 58–66.

[56] F. Z. Peng, J. S. Lai, J. W. McKeever, and J. VanCoevering, “A multilevelvoltage-source inverter with separate DC sources for static var genera-tion,” IEEE Trans. Ind. Applicat., vol. 32, pp. 1130–1138, Sept. 1996.

[57] M. P. Steimer and J. K. Steinke, “Five level GTO inverters for largeinduction motor drives,” inConf. Rec. IEEE-IAS Annu. Meeting, Oct.1993, pp. 595–601.

[58] A. Campagnaet al., “A new generalized multilevel three-phase structurecontrolled by PWM,” inProc. Fourth European Conf. Power Electronicsand Applications, 1991, pp. 235–240.

[59] N. S. Choi, J. G. Cho, and G. H. Cho, “A general circuit topology ofmultilevel inverter,” inProc. IEEE PESC’91, June 1991, pp. 96–103.

[60] T. A. Meynard and H. Foch, “Multilevel converters and derivedtopologies for high power conversion,” inProc. 1995 IEEE 21st Int.Conf. Industrial Electronics, Control, and Instrumentation, Nov. 1995,pp. 21–26.

[61] X. Yuan, H. Stemmler, and I. Barbi, “Investigation on the clampingvoltage self-balancing of the three-level capacitor clamping inverter,”in Proc. IEEE PESC’99, 1999, pp. 1059–1064.

[62] F. Z. Peng, J. W. McKeever, and D. J. Adams, “A power line condi-tioner using cascade multilevel inverters for distribution systems,” inConf. Rec. IEEE-IAS Annu. Meeting, New Orleans, LA, Oct. 1997, pp.1316–1321.

[63] , “Cascade multilevel inverters for utility applications,” inProc.IEEE IECON’97, New Orleans, LA, Nov. 1997, pp. 437–442.

[64] J. W. Kolar, U. Drofenik, and F. C. Zach, “Current handling capacityof the neutral point of a three-phase/switch/level boost-type PWM (Vi-enna) rectifier,” inProc. IEEE PESC’96, Baveno, Italy, June 1996, pp.1329–1336.

[65] K. A. Corzine, J. R. Baker, and J. Yuen, “Reduced parts-count multi-level rectifiers,” inConf. Rec. IEEE-IAS Annu. Meeting, Chicago, IL,Sept. 2001, CD-ROM.


[66] R. Redl, L. Balogh, and N. O. Sokal, “A novel soft-switching full-bridgeDC/DC converter analysis, design consideration, and experimental re-sults at 1.5 kW, 100 kHz,”IEEE Trans. Power Electron., vol. 6, pp.408–418, July 1991.

[67] F. Canales, P. M. Barbosa, and F. C. Lee, “A zero voltage and zero cur-rent switching three-level DC/DC converter,” inProc. IEEE APEC, NewOrleans, LA, Feb. 2000, pp. 314–320.

[68] I. Barbi, R. Gules, R. Redl, and N. O. Sokal, “DC/DC converter forhigh input voltage: four switches with peak voltage ofV in=2, capacitiveturn-off snubber, and zero-voltage turn-on,” inProc. IEEE PESC’98,Fukuoka, Japan, May 1998, pp. 1–7.

[69] G. Beinhold, R. Jakob, and M. Nahrstaedt, “A new range of mediumvoltage multilevel inverter drives with floating capacitor technology,”in Proc. 9th European Conf. Power Electronics (EPE), Graz, Austria,2001, CD-ROM.

[70] M. Koyama, Y. Shimomura, H. Yamaguchi, M. Mukunoki, H. Okayama,and S. Mizoguchi, “Large capacity high efficiency three-level GCT in-verter system for steel rolling mill drives,” inProc. 9th European Conf.Power Electronics (EPE), Graz, Austria, 2001, CD-ROM.

[71] J. Rodríguez, J. Pontt, G. Alzamora, N. Becker, O. Einenkel, J. L.Cornet, and A. Weinstein, “Novel 20 MW Downhill Conveyor SystemUsing Three-Level Converters,” inConf. Rec. IEEE-IAS Annu. Meeting,Chicago, IL, Oct. 2001, CD-ROM.

[72] J. Rodríguez, L. Morán, A. González, and C. Silva, “High voltage mul-tilevel converter with regeneration capability,” inProc. IEEE PESC’99,Charleston, SC, June 1999, pp. 1077–1082.

[73] B. A. Renzet al., “AEP unified power flow controller performance,”presented at the IEEE/PES Winter Meeting, Tampa, FL, 1998, PaperPE-042-PWRD-0-12.

[74] “STATCOM …power electronics on the move,” GEC Alstom T&D,Villeurbanne, France, brochure, 1998.

[75] P. K. Steimer, J. K. Steinke, and H. E. Gruning, “A reliable, interface-friendly medium voltage drive based on the robust IGCT and DTC tech-nologies,” inConf. Rec. IEEE-IAS Annu. Meeting, Phoenix, AZ, Oct.1999, pp. 1505–1512.

[76] S. Eicher, A. Weber, S. Bernet, and P. Steimer, “The 10 kV IGCT — Anew device for medium voltage drives,” inConf. Rec. IEEE-IAS Annu.Meeting, Rome, Italy, Oct. 2000, pp. 2859–2865.

[77] F. Auerbach, M. Glantschnig, A. Porst, J. G. Bauer, D. Reznik, H. J.Schulze, J. Gottert, M. Hierholzer, T. Schutze, and R. Spanke, “6.5 kVIGBT modules,” inConf. Rec. IEEE-IAS Annu. Meeting, Phoenix, AZ,Oct. 1999, pp. 1770–1774.

[78] A. Q. Huang, S. Sirisukprasert, Z. Xu, B. Zhang, and J. S. Lai, “Ahigh-frequency 1.5 MVA H-bridge building block for cascaded multi-level converters using emitter turn-off thyristor (ETO),” inProc. IEEEAPEC, Dallas, TX, Mar. 2002, pp. 25–32.

José Rodríguez(M’81–SM’94) received the Engi-neer degree from the Universidad Técnica FedericoSanta María, Valparaiso, Chile, in 1977 and theDr.-Ing. degree from the University of Erlangen,Erlangen, Germany, in 1985, both in electricalengineering.

Since 1977, he has been with the University Téc-nica Federico Santa María, where he is currently aProfessor and Head of the Department of ElectronicEngineering. During his sabbatical leave in 1996, hewas responsible for the Mining Division of Siemens

Corporation in Chile. He has extensive consulting experience in the mining in-dustry, especially in the application of large drives like cycloconverter-fed syn-chronous motors for SAG mills, high-power conveyors, controlled drives forshovels, and power quality issues. His research interests are mainly in the areasof power electronics and electrical drives. Recently, his main research interestshave been multilevel inverters and new converter topologies. He has authoredor coauthored more than 100 refereed journal and conference papers and con-tributed to one chapter inPower Electronics Handbook(New York: Academic,2001).

Jih-Sheng (Jason) Lai (S’84–M’87–SM’93)received the M. S. and Ph.D. degrees in electricalengineering from the University of Tennessee,Knoxville, in 1985 and 1989, respectively.

From 1980 to 1983, he was the Head of the Elec-trical Engineering Department, Ming-Chi Instituteof Technology, Taipei, Taiwan, R.O.C., where heinitiated a power electronics program and receiveda grant from his college and a fellowship from theNational Science Council to study abroad. In 1986,he became a staff member at the University of

Tennessee, where he taught control systems and energy conversion courses. In1989, he joined the Electric Power Research Institute (EPRI) Power ElectronicsApplications Center (PEAC), where he managed EPRI-sponsored power elec-tronics research projects. In 1993, he joined Oak Ridge National Laboratoryas the Power Electronics Lead Scientist, where he initiated a high-power elec-tronics program and developed several novel high-power converters includingmultilevel converters and auxiliary-resonant-snubber-based soft-switchinginverters. Since August 1996, he has been with Virginia Polytechnic Instituteand State University, Blacksburg, as an Associate Professor. His main researchareas are in high-power electronics converter topologies, motor drives, andutility power electronics interface and application issues. He has authored morethan 100 published technical papers and two books. He is the holder of eightU.S. patents in the area of high power electronics and their applications. Hechaired the Technical Committee for the 2001 DOE Future Energy Challenge.

Dr. Lai is the Chairman of the IEEE Power Electronics Society StandardsCommittee. He is a member of Phi Kappa Phi and Eta Kappa Nu. He was the re-cipient of several distinctive awards, including a Technical Achievement Awardat Lockheed Martin Award Night, two Conference Paper Awards from the In-dustrial Power Converter Committee of the IEEE Industry Applications Society,one IEEE IECON Best Paper Award, and an Advanced Technology Award fromthe Inventors Clubs of America, Inc.

Fang Zheng Peng(M’93–SM’96) received the B.S.degree from Wuhan University, Wuhan, China, in1983 and the M.S. and Ph.D. degrees from NagaokaUniversity of Technology, Nagaoka Japan, in 1987and 1990, respectively, all in electrical engineering.

From 1990 to 1992, he was a Research Scientistwith Toyo Electric Manufacturing Company, Ltd.,where he was engaged in research and developmentof active power filters, flexible ac transmissionsystems (FACTS) applications, and motor drives.From 1992 to 1994, he was a Research Assistant

Professor at Tokyo Institute of Technology, where initiated a multilevel inverterprogram for FACTS applications and a speed-sensorless vector control project.From 1994 to 1997, he was a Research Assistant Professor at the University ofTennessee, Knoxville, working for Oak Ridge National Laboratory (ORNL).From 1997 to 2000 he was a Senior Staff Member at ORNL and Lead(principal) Scientist of the Power Electronics and Electric Machinery ResearchCenter. In 2000, he joined Michigan State University, East Lansing, as anAssociate Professor in the Department of Electrical and Computer Engineering.He is the holder of ten patents.

Dr. Peng has received many awards, including the 1996 First Prize PaperAward and the 1995 Second Prize Paper Award from the Industrial Power Con-verter Committee at the IEEE Industry Applications Society Annual Meeting,the 1996 Advanced Technology Award of the Inventors Clubs of America, Inc.,the International Hall of Fame, the 1991 First Prize Paper Award from the IEEETRANSACTIONS ONINDUSTRY APPLICATIONS, and the 1990 Best Paper Awardfrom theTransactions of the Institute of Electrical Engineers of Japan, and thePromotion Award of the Electrical Academy. He has been an Associate Editor ofthe IEEE TRANSACTIONS ONPOWER ELECTRONICSsince 1997 and is currentlythe Chair of the Technical Committee for Rectifiers and Inverters of the IEEEPower Electronics Society.

Documents

Multi Level Topologies Survey